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Constructional Project
Project by Stefan Keller -Tuberg
This device will disconnect a load from its power
supply if the voltage is reversed or too high. It
also disconnects the load if it draws current
above the adjustable trip level. Its dual-rail
support means it can work with devices like
audio amplifiers with a split (positive and
negative) supply.
I
Dual-Rail
Load Protector
n May 2025, we published three DC
Supply Protectors that guard against
reversed or excessive supply voltages,
but they could only handle a singlerail supply.
This design provides even more functions, extends the reverse/overvoltage
protection to split rails and adds adjustable current limits with automatic
or manual resetting.
If you’ve built something that uses
flying power leads, you may already
have had a close call mixing up polarities. Or have you ever forgotten
to check that you’re using the right
supply to power a device? If any of
these ring true, this design might help
avoid a catastrophe by introducing
power supply protection. It’s so versatile that you’ll think of many applications for it.
The overvoltage cut-out levels can be
set between ±5V and ±19V (or 5-38V
for the single-rail version). If the supply
overshoots the protection level, this
device will rapidly interrupt it.
The overcurrent thresholds are set
by a current sense resistor and trimpot. The sense resistance is chosen
so the voltage drop is approximately
50mV at the nominal protection level.
The trimpot range permits adjustment
from zero up to twice the nominal current level.
When the current limit is reached,
it interrupts the offending power rail
60
by turning it off completely, similar
to a fuse blowing. This minimises the
chance of damage due to a fault compared to simply holding the current
at the threshold by reducing the voltage, as a current-limited bench supply
would do.
Also, if the device is unattended
when it fails, interrupting rather than
limiting the power delivered could help
avoid an even larger disaster.
It can be set so that when the overcurrent circuit trips, it will automatically reconnect after a two-second
delay or require manual intervention
(a button press). If your dual-rail application is asymmetric, you can set
different overvoltage and overcurrent
thresholds for each rail.
Depending on the Mosfets used, it
can handle up to 4-7A per rail without heatsinking. Adding heatsinks to
the Mosfets will allow them to handle
more, up to 10A for the higher-current
Mosfets specified.
Due to the design’s modularity, you
only need to populate the required features. To start with, you can equip it to
suit single or dual supply rails. Configuring it for a single rail saves a few
components and doubles the single
supply maximum voltage to 36V.
If your device to be protected has
more than one positive or more than
Fig.1: some of the different
ways the Supply Protector
can be used. If the maximum
voltage of ±18V for the dualrail version is not enough for
your application, you can
stack two boards to double
that, as shown on the far
right.
Practical Electronics | September | 2025
Dual-Rail Load Protector
Features & Specifications
● Voltage range: 4-36V DC or
±4-18V DC (±4-36V DC with two
boards)
● Over-voltage cut-out: 5-38V DC
or ±5-19V DC (±5-38V DC with
two boards)
● Voltage withstand: up to ±60V
at either input or across both
inputs
● Current capability: 7A+
without heatsinking (more with
heatsinks)
● Voltage insertion loss: typically
<300mV <at> 10A
● Over-current protection:
disconnects rails independently
if current draw exceeds a set
threshold
● Over-current reset: automatically
after two seconds or manually
via pushbutton
🔹
🔹
🔹
🔹 exact values depend on parts used
one negative rail, you can common the
grounds and use two or more of these
boards to protect them all, including
dual-rail applications operating up to
±36V, as shown in Fig.1.
You can leave some components off
if you don’t need overcurrent protection. You can also leave off the overvoltage sections if you don’t want that
feature. The circuit is arranged in three
sections, each supporting one or two
power rails.
Reverse polarity protection
The first section of the circuit, shown
in Fig.2, uses Mosfets Q1 & Q2 like ‘ideal
diodes’. They have a very low voltage
Practical Electronics | September | 2025
drop when forward-biased but a high
impedance when reverse-biased.
If you accidentally connect the input
voltages with the wrong polarity, the
internal body diodes of Mosfets Q1 and
Q2 will be reverse-biased, and no current can flow. Q1 and Q2 remain off,
protecting all the downstream components from the abnormal condition. The
specified Mosfets have reverse voltage
ratings up to 60V, offering plenty of
protection against accidental power
supply reversal.
However, without protection, the
Mosfets could be damaged by gate-tosource voltages exceeding 20V. Zener
diodes ZD1 and ZD2 ensure that the
voltage between the gate and source of
each Mosfet cannot exceed 15V. Other
Mosfets in the design have similar
protections.
When the input voltage polarities
are correct, the internal diodes of Q1
& Q2 are forward-biased. As current
starts to flow, 47kW resistors pull the
Mosfet gates to ground, so they switch
on. As the gate bias exceeds 2-4V and
the Mosfet channel resistance drops,
the internal protection diodes will be
shunted, so very little voltage will be
lost across the Mosfets.
The Supply Protector’s minimum
voltage rating of 4V is because that is
the minimum voltage at which the Mosfets used are guaranteed to switch on
and conduct sufficient current.
Over-voltage protection
The following section deals with
over-voltages. Zener diodes ZD3 and
ZD6 set a fixed value for each rail’s
protection threshold. The knee voltage for 1W zener diodes rated above
5.6V occurs around 3.5-5% below the
nominal zener voltage. As the supply
voltage reaches this level, they will
start to break down. Lower voltage
zener diodes have a more rounded
knee, so the difference from nominal
can be larger.
When enough current flows to develop 0.6V at the gate of the associated SCR, it will trigger and switch off
either Mosfet Q4, in series with the
positive rail, or Mosfet Q5 in the negative rail, disconnecting and protecting
the downstream circuitry and the load.
The SCR will remain latched until
the supply voltage is removed. Providing the applied voltage remains below
the Mosfet specification (55V or 60V),
the unit will tolerate the condition indefinitely, and the device you’re protecting will stay safe.
Most applications won’t require
fine overvoltage threshold adjustment,
so you can simply set it by selecting
the nearest zener. Two extra diodes
labelled D4 and D5, in series with
the zeners, allow the threshold to be
tweaked. Usually, they are replaced
with wire links, but if required, regular or schottky diodes can be fitted to
increase the overvoltage trip thresholds by 0.3V (SB140/1N5819) or 0.6V
(1N4004).
Op amp IC1 has an absolute maximum limit of 40V, the highest overvoltage threshold supported. In practice, the trip points should be no more
than ±19V for one dual-rail device or
38V for a single-rail version, giving a
small safety margin.
The 220μF and 3300μF electrolytic
capacitors are to counteract the effects
of power source inductance. At switchon, many devices cause a momentary
current surge as the supply bypass
61
Constructional Project
Fig.2: the Supply Protector circuit has mostly independent positive and negative sections with three stages each. The
first is reverse polarity protection (using Mosfets Q1 & Q2), followed by overvoltage protection (Mosfets Q4 & Q5), then
overcurrent protection (Mosfets Q10 & Q11). The only sections shared between the positive and negative rails are the
half-supply generator (IC1d), reset oscillator (IC1c) and reset switch.
capacitors charge. This high current
pulse can interact with inductances in
the wiring etc, causing ‘ringing’ (oscillation), which causes an overshoot voltage to appear on the affected power rail,
sometimes a significant one.
One of my test supplies caused
damped oscillations with a frequency of around 2MHz, resulting in a peak
overshoot voltage of around 50% above
the nominal supply. This persistently
tripped the overvoltage protection at
power-on.
The electrolytic capacitors dampen
power-on overshoot to avoid false
overvoltage trips. In severe cases, you
may need to increase the value of the
220μF parts, although they should
be sufficient for most cases. It is usually more severe with a longer input
power cable.
Overcurrent protection
The third section of the circuit pro62
vides overcurrent protection. The load
current is monitored by the voltage
drop across the ‘+sense’ and ‘-sense’
resistors. For the positive rail, LED15,
VR1 and one ‘+bias’ resistor set an adjustable reference voltage at pin 3 of
IC1a that is a couple of volts below the
+ve rail voltage.
LED17 and the other ‘+bias’ resistor create another voltage at IC1’s pin
2 that varies with the ‘+sense’ voltage
drop. IC1a compares these voltages; its
output is low when the sensed current
is below the setpoint, so Mosfet Q10
is usually on. If the current setpoint
is exceeded, IC1a’s output goes high,
switching off Q10 and disconnecting
the load, while also lighting overcurrent indicator LED21. Op amp IC1b,
Mosfet Q11 and LED22 function similarly for the negative rail.
The purposes of LED15 and LED17
aren’t to emit light; they provide
consistent voltage drops so the op
amp inputs remain within the chip’s
common-mode range, which does not
go up to the positive rail. The fact that
LEDs have a higher voltage drop than
a regular silicon diode (around 1.8V
rather than 0.7V) is useful in this application.
The voltage across the ‘+sense’ resistors is approximately 50mV at the
nominal overcurrent trip point. VR1 is
for fine-tuning; its 100W value means
that with 1mA flowing through it, a
full trimpot rotation will cover twice
the nominal voltage range expected
across ‘+sense’.
Note that the ‘+set’ LED (LED15)
usually goes out when the overcurrent
LED (LED21) lights. However, there
are cases where the current is near the
overcurrent set point where both could
light. So if you notice that, it’s normal.
The overcurrent protection only
interrupts the rail experiencing the
overload. When that happens for the
Practical Electronics | September | 2025
Dual-Rail Load Protector
positive rail, D19 provides a feedback
path to latch the state even after Q10
interrupts the current and the ‘+sense’
voltage drop falls back to zero. It will
remain off until the condition is reset
by NPN transistor Q8 switching on
and pulling pin 3 of IC1a below the
pin 2 level.
When the output of IC1a goes high,
another NPN transistor (Q9) inverts
the transition to create a falling edge.
This is combined with any falling
edge from IC1b by diode D24. These
are AC-coupled to IC1c by a 1nF capacitor and diode D29, which works
as an overcurrent reset monostable. A
two-second delay is provided by the
1μF capacitor and 2.2MW resistor. The
100kΩ resistor at pin 9 of IC1c prevents
damaging input currents when pins 9
and 10 differ by more than 5.5V.
When the monostable times out (if
enabled) or the reset pushbutton is
pressed, Q6, Q7 and Q8 temporarily
Practical Electronics | September | 2025
shift the voltage levels at the inputs of
IC1a and IC1b. This forces them out of
their latched states, re-enabling Mosfets Q10 and Q11.
If the auto-reset feature is enabled,
voltage to the load will be restored
two seconds after it trips. If the overcurrent condition persists, the trigger-
delay-restore process will repeat indefinitely every two seconds (or until
the fault clears).
This monostable arrangement requires a reference voltage at the midpoint of the IC’s power supply. We
could have used the GND line for this
reference, but that would mean the
circuit would only work with symmetrical dual rails, reducing its flexibility. So IC1d synthesises a mid-rail
voltage (halfway between +ve and -ve)
that self-adjusts without needing different configurations.
The 100nF capacitor and 1MW resistor connected to header CON3
ensure that resets are only momentary, even if the pushbutton is held
down. This quickly rearms the overcurrent protection while preventing
the output from being held on continuously if excessive current continues to flow. The 100nF capacitor
at IC1c’s output works similarly for
monostable-initiated resets.
We don’t care about the brightness
of LED15-LED18 since, as mentioned,
they are not indicators. However, it
does matter for LED7, LED8, LED21
and LED22. The circuit shows 22kW
current limiting resistors for them, suiting high-brightness LEDs. If using regular LEDs, reduce the values to around
5.6kW for more current.
Alternatively, if they’re too bright
(which may happen with higher-voltage
single-rail applications), increase the
series resistances.
Diodes D26 and D27 across the
output terminals are normally reverse-
63
Constructional Project
biased. These protect the circuit from
inductive loads or long output power
leads. Any inductance in these can
cause a reverse voltage spike when
the load current is interrupted (as can
certain capacitor configurations in the
load). These diodes will safely dissipate that energy.
Component selection
The PCB is designed for miniature
1/8W resistors, 3.5mm long. You can
get them from element14, DigiKey or
Mouser. You can use more common 1/4W
resistors, but you will need to stand
them up (at least partially).
The current sense resistors will
typically be below 0.1W. element14,
DigiKey and Mouser have wide ranges
of low-value ‘current sense’ resistors,
many of which will be suitable, even
if their power ratings are higher than
necessary. Alternatively, parallel two or
more resistors to create a lower resistance. The PCB holes are large enough
for the leads of current-sense resistors
or multiple regular resistors.
The parts list gives information on
supported capacitor lead pitches (although you can bend them if you have
to) and suggested Mosfet types. However, many more suitable ones will be
available.
If substituting other Mosfets, pay
particular attention to their maximum
on-resistance, Vgs threshold voltage and
reverse breakdown voltage. Particularly for P-channel Mosfets, cost-effective
options with a low on-resistance aren’t
common. The higher the maximum
on-resistance, the hotter the Mosfets
will run.
Heatsinking
Using, say, IRF1018E and IRF4905
Mosfets, at 4A current draw and 10V
or higher, they will dissipate 135mW
and 320mW each, respectively. The
temperature of a TO-220 package in
free air rises by around 70°C/W, so
without heatsinking, they will rise to
9°C and 22°C above ambient.
Note that the ambient temperature
is the air temperature within the enclosure, which could be significantly
higher than room temperature.
The Mosfet on-resistances could be
a little higher when using rail voltages
significantly below 10V, so for lower
operating voltages, pay close attention
to the Mosfet temperatures during testing. If they become too warm to touch
comfortably, they require heatsinks.
If you know or suspect you’ll need
heatsinks in advance, it will be easiest
to fabricate and mount the transistors
onto them before soldering the transistors to the PCB.
You can fashion heatsinks from 3mm
aluminium using three separate bars
or angles for the three rows of Mosfets. Cut the material to fit comfortably
within the component footprint. For a
dual rail application, mount two Mosfets per angle with their centre holes
spaced 18mm apart. Use insulators
and Nylon bushes and/or screws; insulating each Mosfet from its heatsink
is the best practice.
You won’t necessarily require large
heatsinks; it depends on how much
power needs to be dissipated. For maximum heat dissipation, bridge the tops
of the three aluminium angles with a
commercial heatsink.
Construction
Figs.3 & 4: the dual-rail version of the Supply Protector uses all the parts on
the PCB, although some sections can be omitted. Parts that can be left off if you
don’t need over-current protection are shown, in Figs.7 & 8. Soldering heavyduty 1mm2 wires to the underside of the board, as shown here, will reduce
the resistance of the current-carrying tracks. That will lower the voltage drop
between the input and output and allow the PCB to handle more than 5A.
64
Start by selecting the values of the
current sense and bias resistors, and
over-voltage threshold zeners, using
either the panel or Tables 1 & 2 overleaf.
The Supply Protector is built on a
double-sided 96 × 69mm PCB coded
18109241. If you’re building the full
dual-rail version, fit all the components shown in Fig.3, while if you
want to make the single-rail version,
fit just the components shown in Fig.5
or Fig.6. Figs.7 & 8 show further variations, which experienced constructors
Practical Electronics | September | 2025
Dual-Rail Load Protector
could combine with one of the single-
rail variants if desired.
The two adjustment diodes, D4
and D5, are generally not required
and can be replaced with wire links.
If you need to fine-tune the trip voltage, you can fit diodes instead, as explained earlier.
We suggest constructing in two
stages: build and test the reverse-
polarity and overvoltage protection
sections before adding the remaining
components. Roughly speaking, the
reverse and overvoltage protection
components are below and to the left
of the 3300μF electrolytic capacitor in
the middle of the board, not including
the two 3300μF capacitors (use Fig.7
as a guide).
Pay close attention to the orientation of the transistors, diodes, LEDs
and electrolytic capacitors. The two
SCRs should face in opposite directions. Start by fitting the lowerprofile components like the diodes
and resistors that will lie flat on the
board (see Table 3), then the capacitors, then the taller components like
the Mosfets.
If you want to minimise the voltage drop across the device, or will be
using it at high currents, you can solder
extra wires to the underside as shown
in Fig.4. That should not be necessary
for applications up to around 5A per
rail, though.
Initial testing
The easiest way to verify the correct
operation of the reverse polarity protection is with a variable power supply.
Apply power to the input connector
in reverse but starting at 0V. Ramp the
voltage slowly up to -1V and monitor
the “+rail” and “–rail” test points with
a multimeter to verify the absence of
any voltage. It is working if the supply
reaches -1V and there is no voltage on
those test points.
You could use one AA or AAA cell if
you don’t have a variable power supply.
Note that if you previously applied
power in the correct direction, your
multimeter may read the residual
charge on the 220μF capacitors.
Next, verify the overvoltage protection threshold by switching off the
variable power supply and reconnecting the supply with the correct polarity. As you ramp the variable power
supply up, by the time it reaches 1V,
a voltage will be detectable on both
test points.
Practical Electronics | September | 2025
The fully assembled Dual Rail Supply Protector PCB with all features available.
Note the use of smaller-than-usual resistors to keep it compact.
Figs.5 & 6:
these overlay
diagrams
shows the
board fitted
with just the
components
needed for
a single
rail Supply
Protector.
You need
to add wire
links where
shown in
red. When
building
any of these
versions,
watch the
orientation of
the IC, diodes
and Mosfets,
as they must
all be correct.
65
Constructional Project
Pluggable terminal blocks for the inputs
and outputs make connecting the wires easy.
The board can be mounted using a tapped
spacer in each corner.
Figs.7 & 8:
these
overlays
shows which
components
you can
leave off (or
link out) if
you don’t
want either
the overcurrent or
over-voltage
protection
feature. If
building a
single-rail
version, you
will need to
refer to Figs.5
& 6 as well,
and figure
out which
components
to leave off or
link out.
66
The readings will initially be around
0.7V below the variable power supply
level. Once you reach 3-4V, the test
point voltages should rise to the input
voltage.
There are two additional test points
labelled “+rail prot” and “–rail prot”,
which you can now monitor. Continue increasing the variable supply towards the protection threshold. As
you pass the threshold, each overvoltage protection LED should illuminate and then, at a fractionally
higher input voltage, the “+rail prot”
and “-rail prot” test points should start
falling back to zero.
The actual tripping thresholds may
differ from the calculated value due to
component tolerances and the zener
knees.
Remember not to ramp the input
voltage past the ratings of the 220μF
capacitors, and be very careful not to
ramp your variable supply past 40V (or
±20V) until you are sure the overvoltage protection in both rails is working
correctly, or you risk damaging IC1 (if
fitted). If either rail’s protection hasn’t
kicked in by 1V beyond the calculated
trip point, it’s either not working, or
the zeners are wrong.
To reset after the overvoltage protection has tripped, return the variable supply to 0V or temporarily disconnect it.
With the overvoltage protection section working, you can finish fitting
components to the PCB, starting with
IC1; ensure its pin 1 indicator goes at
upper right as shown in the overlay
diagram. Don’t mount the two trimpots yet.
If your board needs cleaning because
it’s covered in flux residue, submerge
it under isopropyl alcohol or methylated spirits and gently rub it with an
old toothbrush. Wait for it to dry, then
mount and solder the trimpots.
Check that Mosfets are electrically
isolated from any heatsink metal.
To verify the overcurrent trip circuit,
connect the power rail (or rails) to a
variable supply but don’t yet connect
a load. Adjust the power supply to the
same voltage you used to calculate
the bias resistances. If either overcurrent trip LED is already illuminated,
slowly wind the trimpots clockwise
until they extinguish automatically,
use the pushbutton reset or short the
upper two pins of CON3.
If either of the overcurrent trip
LEDs fails to extinguish, there is a
Practical Electronics | September | 2025
Dual-Rail Load Protector
problem with the reset or overcurrent circuit.
If you’re using auto-reset, check the
output of IC1d at the “VG” (virtual
ground) test point is near ground level
for a symmetrical dual-rail version, or
otherwise approximately midway between the power rails.
Assuming both overcurrent LEDs are
off and the set LEDs are on, wind each
trimpot anti-clockwise until either the
trimpot is fully anti-clockwise or the
corresponding set LED switches off and
the overcurrent LED comes on. When
you’ve reached this point, nudge the
trimpot clockwise (and press the reset
button if equipped) so both the overcurrent LEDs are again off.
The overcurrent protection circuits
will now be armed at a very small
current threshold. Use a low-value
resistor (say 100W or less) between
ground and each output rail to verify
that the overcurrent protection triggers. The corresponding overcurrent
LED should illuminate instantaneously, and the associated set LED
should extinguish.
If your overcurrent trip point exceeds the normal operating current
by an amp or more, connect a dummy
load that will draw current just below
the overcurrent tripping point and
adjust VR1 and VR2 so the load remains turned on. Otherwise, use your
intended load to set the overcurrent
trip point.
Finally, run the device for ten minutes while monitoring the temperature
of the Mosfets. If the Mosfets become
too warm to touch comfortably, turn
off the power and fit heatsinks before
using it. Wire it up, and you can sit
back and relax, knowing your load
device is protected!
Parts List – DC Supply Protectors (all features)
1 double-sided PCB coded 18109241, 96 × 69mm
2 100W miniature top-adjust trimpots (VR1, VR2)
2 3-way 5.08mm pitch pluggable terminal blocks (CON1, CON2)
[Farnell 3797901 + 2452499 or DigiKey 5EHDVC-03P + 5ESDV-03P]
1 3-way pin header and jumper shunt (CON3)
1 NO momentary pushbutton (optional)
4 M3 × 6mm panhead machine screws and matching spacers
Semiconductors
1 NCS20074 quad rail-to-rail output op amp, SOIC-14 (IC1)
3 high-current P-channel Mosfets, TO-220 (Q1, Q4, Q10) ★
3 high-current N-channel Mosfets, TO-220 (Q2, Q5, Q11) ★
2 BC556 45V 100mA PNP transistors, TO-92 (Q3, Q7)
3 BC546 45V 100mA NPN transistors, TO-92 (Q6, Q8, Q9)
2 C106 SCRs, TO-126 (Q12, Q13)
8 high-brightness 3mm LEDs (LED7-8, LED15-18, LED21-22)
[Vishay TLLK4401]
6 15V 1A zener diodes, DO-41 (ZD1, ZD2, ZD11, ZD12, ZD23, ZD25)
2 1A zener diodes, DO-41, values to suit application – see Table 1 (ZD3, ZD6)
2 1N5819 or SB140 40V 1A schottky diodes (D13 & D14)
6 1N4148 75V 200mA diodes, DO-35 (D19-D20, D24, D28-D30)
2 1N4004 400V 1A diodes, DO-41 (D26, D27)
2 extra diodes to fine-tune over-voltage thresholds (D4, D5; optional, see text)
★ suitable types include IRF4905 (up to ±55V & 4A),
IPP80P03P4L-07 (±30V & 7A) and SUP90P06-09L-E3 (±60V & 7A)
★ suitable types include IRF1018E (7A), CSD18534KCS (7A), DIT050N06 (4A),
STP60NF06 (5A) & IPP80N06S4L (8A; all can handle up to ±60V,
ratings are without heatsinks and are only a guide)
Capacitors
2 3300μF 50V electrolytic (5mm or 7.5mm lead pitch, diameter ≤ 18mm)
2 220μF 63V low-ESR electrolytic (3.5mm or 5mm lead pitch)
1 1μF 50V ceramic or MKT
9 100nF 50V ceramic or MKT
2 10nF 50V ceramic or MKT
1 1nF 50V ceramic or MKT
Resistors (all ⅛W 5% miniature axial unless noted) ♦
1 2.2MW
9 47kW
4 3.3kW 1W 5%
3 1MW
9 22kW
2 910W
1 330kW
1 15kW
4 Rbias resistors – see Table 1
2 150kW
6 10kW
2 Rsense resistors – see Table 2
3 100kW
♦ regular ¼W resistors can be used but they won’t sit flat on the PCB
Table 1 – zener diode values
Table 2 – current sense resistors
Trip
ZD3/ZD6
Bias resistors
Adjustment range
Sense resistor
~5V
5.1V
3.0kW
0-1A
100mW 1/8W
~5.5V
5.6V
3.3kW
0-2A
50mW 1/4W
~7.25V
6.8V
5.1kW
0-3A
33mW 1/4W
~10.3V
10V
8.2kW
0-4A
25mW 1/2W
~13V
13V
11kW
0-6A
16mW 1/2W
~15.1V
15V
13kW
0-8A
12mW 2/3W
~18V
18V
16kW
0-10A
10mW 1W
~20V
20V
18kW
~23.8V
24V
22kW
~29.5V
30V
27kW
Tables 1, 2 and the panel on the next
page are used to determine the best
values of various components to suit
your needs.
~38V
39V
36kW
Practical Electronics | September | 2025
Table 3 – resistor colour codes
67
NEW!
Constructional Project
Calculating component values
Several component values should be selected to suit your application as follows.
Overvoltage trip point
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First, you must determine the highest voltage that’s safe to apply to the
load. If unsure, measure the output of the existing power supply and add a
safety margin.
Zener diodes ZD3 (‘+OVtrip’) and ZD6 (-OVtrip’) set the overvoltage trip point
for each rail in combination with the 3.3kW resistors. The SCRs will trip when
their trigger input reaches approximately 0.6V. Allowing for a voltage drop of
about 100mV across the resistors, the required zener voltage is (Trip – 0.7V)
× 1.05.
As mentioned earlier, low-voltage zeners may trigger at lower voltages than
expected. Also, typical zeners diodes have 5% tolerances.
In the middle of the voltage range (eg, around ±15V), you can generally get
away with a zener diode that has a voltage rating close to the desired trip point,
as the 0.7V and 5% factors cancel out.
Because the expected overvoltage trip point lies within a range, and zeners
are only available in certain preferred values, you may need to use adjustment
diodes if you require high precision. Adding a schottky diode for D4 or D5
(like a BAT85, SB140 or 1N5819) will increase that rail’s trip point by around
0.3V, while adding a silicon diode (like a 1N4148 or 1N4004) will increase it
by around 0.6V.
Don’t use zeners below 4.3V or above 19V (for a dual-rail configuration) or
39V (for single-rail operation). You can use different values for the two zeners
for asymmetric applications.
Ensure that the 3300μF output capacitors have voltage ratings above the
trip points. For example, if you have ±18.1V overvoltage protection thresholds,
select 25V capacitors.
Because the 220μF capacitors after Mosfets Q1 & Q2 are on the unprotected
side of the overvoltage protection circuit, they will experience any overvoltage,
so their voltage ratings should exceed the highest expected input voltage. We
recommend using 50V or 63V rated capacitors there, although you might get
away with 35V caps in some cases.
Overcurrent trip point
The ‘+sense’ and ‘-sense’ resistors are used to monitor the current in each
rail. The overcurrent trip is calculated for a sense resistor voltage drop of about
50mV, although the trimpots let you set it up to 100mV.
Use Ohm’s law, R = V/I, and the power formula, P = VI, to calculate the required
resistances and power ratings. Let’s use 2A as an example. For a 50mV drop,
the formulas give R = 25mW (0.05V ÷ 2A). If you can’t find a resistor with the
calculated value, round the resistance to the closest available value. A 0.022W,
0.025W or 0.033W resistor would be suitable in this case.
We calculate the power at 100mV as we don’t want the resistor to overheat
if the trimpot is set to maximum, so P = 200mW (0.1V × 2A). Ideally, the resistor should have close to twice the power rating (to account for elevated ambient temperatures etc), so in this case, use a ½W or 0.6W resistor.
If your application has asymmetric current requirements, you can choose
different values for the two resistors.
Bias resistances
Four resistors are labelled ‘+bias’ or ‘-bias’. The bias resistors are selected
so that about 1mA flows through them when the supply is at its nominal (not
overvoltage trip) level.
The series LEDs have a forward voltage drop of around 1.8-2V, so consider
that when calculating the resistor values. The exact drop doesn’t matter as
long as the four LEDs (LED15-LED18) are the same type, so the voltage drops
are similar. Red, orange or yellow LEDs with a forward voltage drop below
2.3V will work.
You can measure the LED’s forward-biased drop using a digital multimeter’s
diode testing function.
Say the nominal power supply is ±12V and you have red LEDs with a 1.6V
forward voltage. The required resistance will be R = (12V – 1.6V) ÷ 0.001A =
10.4kW. Choose the nearest available resistance, 10kW in this case.
If you have an application with asymmetric voltage rails, the ‘+bias’ and
PE
‘-bias’ resistances may differ.
Practical Electronics | September | 2025
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