This is only a preview of the July 2025 issue of Silicon Chip. You can view 37 of the 104 pages in the full issue, including the advertisments. For full access, purchase the issue for $10.00 or subscribe for access to the latest issues. Articles in this series:
Articles in this series:
Items relevant to "The SmartProbe":
Articles in this series:
Items relevant to "Hot Water System Solar Diverter, part two":
Items relevant to "Low-cost electronic modules: 8×16 LED Matrix module":
Items relevant to "SSB Shortwave Receiver, part 2":
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JULY 2025
ISSN 1030-2662
07
The VERY BEST DIY Projects!
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The SmartProbe
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Solar USB Charging
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Contents
Vol.38, No.07
July 2025
14 SpaceX
Page 33
SpaceX is the world leader for space launch services (crew transportation,
satellite launches etc). They have been responsible for dramatically
reducing the cost of access to space. Here is how they have done it.
By Dr David Maddison, VK3DSM
Aerospace technology
46 Precision Electronics, Part 9
We have now reached the final part of our series on precision electronic
systems. We summarise the building blocks that we have already covered
and provide an example of how to design a whole system.
By Andrew Levido
Electronic design
54 Salvaging Parts
SmartProbe
Precision Electronics
Part 9 – Page 46
There’s a lot of useful parts and components that can be harvested from
discarded consumer goods like washing machines, printers, photocopiers,
drills etc. Here’s what you should look out for.
By Julian Edgar
Reusing & recycling
Page 54
70 8×16 LED Matrix module
These LED matrix panels are bright (with just 400mW power consumption),
compact and relatively easy to drive. They use an AIP1640 driver IC which
can be controlled via a protocol that is similar to I2C.
By Tim Blythman
Low-cost electronic modules
26 Solar Charging via USB
Here’s how to charge and power all your devices from solar power, using
a low-cost system. It’s easy to build, and can even be built as a portable
system or wired up in your home.
By Julian Edgar
Simple electronic project
33 The SmartProbe
This little device is ideal for taking voltage and continuity measurements.
It measures up to ±50V and tests diodes/LEDs/forward voltages. It is
powered by a single CR2032 cell.
By Andrew Levido
Test & measurement project
62 Hot Water System Solar Diverter
Using this device can save you a lot of money! It lets you use excess solar
power generation to power your electric water heater. The final part in this
series covers the construction, setup & testing.
Part 2 By Ray Berkelmans & John Clarke
Solar energy project
74 SSB Shortwave Receiver, Part 2
Covering the entire shortwave band, this Receiver is digitally tuned and has
a bunch of helpful features like squelch, LSB/USB support, good sensitivity
and more. We cap things off by showing you how to build, test & align it.
By Charles Kosina
Radio receiver project
SALVAGING PARTS
2
Editorial Viewpoint
5
Mailbag
53
Subscriptions
80
Circuit Notebook
82
Serviceman’s Log
88
Vintage Radio
97
Online Shop
100
Ask Silicon Chip
103
Market Centre
104
Advertising Index
104
Notes & Errata
1. GPS Speedometer
2. Logic level indicator
Eddystone EC10 Mk2 by Ian Batty
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Silicon Chip
Editorial Viewpoint
Confusion between lithium
battery types
It has become very common for people to refer to
lithium-ion batteries as “lithium batteries”, but that is
confusing since lithium metal batteries existed before
lithium-ion batteries were invented, and they are quite
different.
The term “lithium battery” used to specifically refer
to a disposable battery that used lithium metal as the
anode. These have been around since the 1970s and are still widely used in
applications where long shelf life and high energy density are important, such
as memory backup, smoke alarms and small medical devices.
They come in various chemistries, like lithium-manganese dioxide, lithium-
thionyl chloride, lithium-iron disulfide, and so on. Those all share one critical
feature: they are not rechargeable.
In contrast, lithium-ion batteries are rechargeable and use a lithium compound rather than metallic lithium. The lithium atoms give up an electron to
become positively charged ions, which move between compounds in the electrodes during charging and discharging – hence the name.
Though their chemistry is more complex and sensitive than lithium-metal
batteries, their energy density and rechargeability have made them the dominant choice for everything from phones to electric vehicles.
In fact, what we call “lithium-ion batteries” is a whole family of different
chemistries with similar, but not identical, properties. Common lithium-ion
chemistry variants include lithium cobalt oxide (LiCoO2), lithium nickel manganese cobalt oxide (LiNiMnCoO2), lithium nickel cobalt aluminium oxide
(LiNiCoAlO2), lithium manganese oxide (LiMn2O4) and lithium iron phosphate (LiFePO4).
You may be familiar with that last one because it has more significantly different properties from most of the others, such as a lower terminal voltage, plus
better tolerance for over-charging and over-discharging.
Getting back to my main point, why the confusion between lithium-ion and
lithium batteries? Somewhere along the line, “lithium-ion battery” got shortened; first in casual conversation, then in journalism, and now even in marketing. The problem is that “lithium battery” still means something else in
technical contexts.
The distinction especially matters in transport: postal and courier rules, particularly for air freight, can differ significantly between lithium and lithium-ion
batteries. It doesn’t help that many consumer devices now include vague labels
like “contains lithium battery”, even on products that clearly use lithium-ion
cells. This ends up muddying the waters for everyone else.
The distinction is especially important when it comes to charging. Try to
charge a non-rechargeable lithium battery and you’re asking for trouble. The
internal chemistry isn’t designed to handle reverse current, and the result can
be catastrophic: swelling, leakage, or even fire.
It is not just theoretical; there have been fires caused by consumers mistakenly trying to recharge lithium primary cells, often due to this exact terminological conflation.
We all sometimes refer to a cell as “a battery” when (arguably) batteries contain more than one cell, but that’s a minor point. Not so the distinction between
lithium and lithium-ion batteries.
So let’s make a collective effort to be more precise. Use the term “lithium-
ion” (or even better, the specific chemistry) to refer to rechargeable batteries.
If you’re referring to a lithium-metal primary cell, it’s best to be explicit, but
if you must call anything a “lithium battery”, it should be those types only.
Cover Image: Steve Jurvetson – www.flickr.com/photos/
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Australia's electronics magazine
by Nicholas Vinen
siliconchip.com.au
MAILBAG
your feedback
Letters and emails should contain complete name, address and daytime phone number. Letters to the Editor are submitted on the condition that
Silicon Chip Publications Pty Ltd has the right to edit, reproduce in electronic form, and communicate these letters. This also applies to submissions to “Ask Silicon Chip”, “Circuit Notebook” and “Serviceman’s Log”.
The ups and downs of grid-scale solar power
I’ve just been reading the articles entitled “The Future
of our Power Grid” (March & April 2025; siliconchip.au/
Series/437).
I noticed the diagram on page 38 of the April issue,
which shows a period in South Australia where it is
claimed that 100% of the grid demand was being met
100% by rooftop solar. The article doesn’t mention that
on the 10th of September last year, only 2% of the South
Australian grid was from renewables – 1% from batteries
and 1% from wind.
Also, I understand that the South Australian grid is now
the most expensive in Australia because of its high levels
of renewables. A recent check showed that whereas we are
paying about 25¢/kWh here in Sydney for our electricity,
my friend with a private home in Adelaide is paying 50¢/
kWh. This is an important issue, and it is one of the reasons that I support nuclear power.
I think it is really important that you give the full story
in any of these articles. I’m sure you will agree.
Dick Smith, Terrey Hills, NSW.
The article’s author, Brandon Speedie, replies: Fig.22 was
intending to show the value of spinning reserve; with high
renewable penetration, some gas is still needed in South
Australia for grid stability.
Your figure from September 10th illustrates a different but
equally important point: there are periods when wind and
solar generation are low. This is why dispatchable capacity is so important (see part 1, in the March edition). South
Australia’s dispatchable capacity is mainly gas, which is
very effective in this role given its speed.
Nuclear is well suited to providing spinning reserve, but
is of limited value as dispatchable capacity, given its operational constraints. This is the same problem our existing
coal generators are struggling with.
As for your South Australian friend, I think they are
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getting ripped off. The state often has the lowest wholesale
prices in the country, so if they are paying more than the
national average, they are getting a raw deal on their retail
agreement and should look for another plan.
Interestingly, the state has long periods of negative
wholesale prices, which is spurring interest from industry
to build plants previously priced out of the market. BHP
is one example; their plans to expand copper production
would double the load on the SA grid.
Separately, I thought you might enjoy hearing a personal anecdote. My Grandfather, a surveyor, was introduced to electronics by building DIY kits from Dick Smith
Electronics. He passed the hobby onto me, a vocation
I now call a career. He died recently, but would have
enjoyed reading this exchange in the pages of his favourite magazine.
Free software for drawing digital waveforms
I recently came across WaveDrom, a digital timing diagram (waveform) rendering engine that uses JavaScript to
convert a JSON description into an SVG vector image file.
I thought this may be of interest to your readers. The software can also run on PC or laptop, although some installation is required. See the following websites:
• https://wavedrom.com/
• https://wavedrom.com/tutorial.html
• https://github.com/wavedrom/wavedrom
The web page says “WaveDrom is a Free and Open Source
online digital timing diagram (waveform) rendering engine
that uses JavaScript, HTML5 and SVG to convert a WaveJSON input text description into SVG vector graphics.” I
have provided a copy of the sample images from the second link (shown below).
Joseph Goldburg, Microchip Technology.
Probe cases are plastic, not metal
Thanks for publishing my letter on the proposal to make
cases for the Current & Differential Probes on page 8 of the
May 2025 issue. I think there has been a misunderstanding as the proposed boxes are not made from metal. This
confusion likely stems from my mentioning heat-treated
tool steel jigs in my emails.
Shearwater dissuaded me from that as it would be
cheaper to get them to mill out the plastic boxes directly.
More boxes would mean a better price per box.
6
Silicon Chip
Shearwater did a good job of milling the six plastic boxes
and end plates. The slide switch opening came out very
nice with half-millimetre radius corners. It cost me $450
for the six (three of each project) boxes and end plates that included the CNC programming. Future orders would
be cheaper because the program has already been done.
The cost per box would basically depend on how many
they would do in a batch. It would be nice to know if any
readers were interested in plastic boxes, and how many.
Michael Vos, Taree, NSW.
More on “The future of our power grid”
In the second part of this series, on page 38 of the April
2025 issue (siliconchip.au/Series/437), there is a note that
I will paraphrase: “100% rooftop solar, all other generators being off aside from a small amount of wind, solar
and Torrens Island Gas steam which was providing grid
stability.”
They are not shown on the Open Electricity data in Fig.22
because the outputs are not metered, but South Australia
has four synchronous condensers, two at Davenport (Port
Augusta) and two at Robertstown. These were built to cover
the loss of grid system strength following the closure of
Augusta Power Station in 2016.
Each synchronous condenser provides 575MVA nominal 275kV fault capability and 1100MW of inertia. That is
equivalent to the inertia created by a 275MW steam-driven
synchronous generator.
Other states and territories in Australia have built or are
building synchronous condensers to cover the shortfalls in
system strength as solar, wind and battery inverter-based
resources (IBR) replace synchronous generation. Here are
some synchronous condenser projects in NSW and Victoria that can be found with a quick internet search:
• Victorian Ouyen 600MVA was completed in 2020,
while the Ararat synchronous condenser is expected to be
in service this year. The AEMO Victorian System Strength
Requirement July 2023 report suggests a further eight
250MVA units are required.
• NSW Transgrid has forecast a further 14 synchronous condensers are required to provide appropriate system strength.
While inverters (IBRs) can contribute to frequency and
voltage control, their effectiveness at grid scale is somewhat unknown.
AEMO released a technical note in September 2024 titled
“Quantifying Synthetic Inertia of a Grid-forming Battery
Energy Storage System” (siliconchip.au/link/ac6g) to determine the future role of IBRs in grid stability.
A video published by the IEEE in July 2023 titled “Power
System Stability With a High Penetration of Inverter-Based
Resources” (https://youtu.be/-hH23MI4Npc) discusses
some unique IBR behaviours that, in some cases, adversely
affect grid stability.
Another consideration is the fault ride-through capability. Fault ride-through is the ability to withstand rapid
changes in load, either due to the loss of generation plants
or line faults.
Synchronous generators and synchronous condensers
typically supply 500% more power than their rated nameplate capacities for short periods and 200% for 30 seconds,
while an IBR typically supplies 120% of its rated nameplate for short periods.
Australia's electronics magazine
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If the fault ride-through capabilities are insufficient,
the grid voltage is likely to fall below the low-voltage trip
points of nearby generators during a fault, causing those
generators to trip. The remaining generators connected to
the grid will then be overwhelmed by the demand and will
trip on either under-voltage or low frequency.
Low fault ride-through capabilities caused the 2016 South
Australia state-wide blackout. The decommissioning of the
Augusta Power Station a few months earlier, and the delay
of the proposed synchronous condensers project, resulted
in the loss of fault ride-through capabilities on the SA grid
(siliconchip.au/link/ac6h).
The system strength in the NEM is explained in the PDF
at: siliconchip.au/link/ac6i
The Victorian System Strength Requirement from July
2023 is in the PDF at: siliconchip.au/link/ac6j
NSW Transgrid turns to synchronous condensers to safeguard system strength, build 14 synchronous condensers:
siliconchip.au/link/ac6k
Mathew Prentis, Port Augusta, SA.
Simple trick for checking CR2032 cells
I was reading the Versatile Battery Tester article in the
May 2025 issue (siliconchip.au/Article/18121) and it
reminded me of how I worked on computers from time to
time, and one problem was flat CMOS batteries (cells). Any
time I wrecked an old PC, I tested the CR2032 cell to see if
it had enough life left to warrant keeping it.
I often found cells that read just over 3V, but that initial
test of the voltage did not indicate how charged the cell
was. So I would use a 3V LED to check that. If the cell was
good, the LED would light up brightly. If the LED lit dimly,
then the cell was no good. This was a convenient way of
determining the overall condition of the cell.
Some time ago, a friend sent me a really good battery
(cell) tester that indicates the voltage, internal resistance
and the percentage of life the cell has remaining.
Last year, our son was overseas, and he left his vehicle
with us, for us to take in for a service while he was away.
He gave us his spare remote to use. I tried to access the
vehicle, but the remote did not work. I suspected that the
cell might be flat, but I had to search online to find out how
to open the remote. Once I got it open, I tested the button
cell with my multimeter and it showed full voltage.
I then got out the battery tester and it showed that the cell
8
Silicon Chip
was almost dead flat. So, as you pointed out in the article,
the terminal voltage of a cell or battery is not an indication
of the charge left in the cell or battery. That demonstrates
the need for a dedicated tester like the project in Silicon
Chip, or the commercial unit that my friend sent me.
Bruce Pierson, Dundathu, Qld.
Help wanted fixing analog meter movements
I am a prolific restorer of valve radios, and my testing
equipment ‘arsenal’ consists of several analog meters of various types (mainly multimeters & VTVMs). Unfortunately,
many of the meter movements are a bit sticky. I want to
find with someone who has the skills to repair these for
me – probably one or two at a time.
I am very much ‘old school’ and I absolutely love my
analog meters. I have been trying to find someone who is
able to help for many years, without success.
Peter Walsham, Auckland, New Zealand.
Feedback on Capacitor Discharger project/kit
Thought I would share a photo of the finished Capacitor
Discharger (December 2024; siliconchip.au/Article/17310)
I made from the kit I bought from you. Even though it’s a
simple kit, just the drilling and fitting took me a while. A
step drill bit was handy to drill the banana plug socket
holes in the ends. My soldering is a little rough; however,
it goes together and works.
The instructions were pretty good in the magazine. I
understand basic operation of the Mosfet and the purpose
of the three resistors and bridge rectifier, but it makes me
appreciate that learning even the basics of electronics is
hard.
The red LED comes on at about 8V DC and above. At
10.7V, it draws 19mA from my bench power supply. I
guess it will discharge the capacitor down to 8V and then
the last 8V you can discharge with a resistor. I just need to
make up a label on my laminator at work.
I enjoy these simpler kits that are you are selling, as I
can’t be bothered buying up all the parts myself as I’m timepoor and they don’t take months to put together.
Edward Menzies, Kew, Vic.
Comment: you would need to use a resistor or similar if
you have to completely discharge the capacitor. The idea
is that, once the capacitor is discharged to 8V, it is no longer hazardous to work on the equipment.
Australia's electronics magazine
siliconchip.com.au
siliconchip.com.au
Australia's electronics magazine
July 2025 9
This is especially useful in cases like switch-mode power
supplies where capacitors are charged up to rectified mains
voltages (~325V DC) and can retain that charge for hours
or even days.
The perils of cloud storage
I would like to add to what D. T. of Sylvania wrote in
the letter titled “Windows’ built-in ‘cloud’ services are a
problem”, on page 8 of the May 2025 issue. I stopped using
OneDrive some years ago. It was originally another drive
on your PC, but then they changed this to synchronise all
documents, and that’s when I disconnected it.
My new Windows 11 PC came with OneDrive enabled
and, after some searching, I disabled it. My PC now shows
‘the cloud’ with a cross through and all greyed out.
Of significant concern is that OneDrive is very vulnerable for those users who have had their Microsoft account
stolen, as happened to me recently. I noticed that the email
address listed in my account wasn’t mine. Trying to recover
this resulted in the hacker continuously resetting my Microsoft account address and phone number.
I contacted the Microsoft chat line and, after 2.5 hours
with an amazing person, they could see the active hacker
also at their end. Eventually, they closed my account. The
problem is that all the cloud data is wiped immediately
when your account is closed. This is the same for Google
Cloud services.
So never use a ‘cloud’ service for any critical data, unless
you have direct access and control of it.
Braham Bloom, Russell Lea, NSW.
Character Map has a search feature
Based on the May 2025 editorial on WinCompose, the
Editor obviously doesn’t like using the Windows built-in
Character Map program. Did you know it is possible to
search for glyphs in Character Map? If you check the
“Advanced view” checkbox, you can search for glyphs
using the “Search for” field.
For instance, if using the Arial font, a search for “greek
omega” will result in 46 choices related to the Greek letter Omega.
John Elliot V, Blaxland, NSW.
Nicholas comments: I have been using Character Map
since Windows 3.11 and had no idea that such a feature
had been added! Apparently that happened with Windows
2000. It’s baffling that such an important tool is hidden
behind an “Advanced view” setting. I still find WinCompose quicker and much more convenient, but this makes
Character Map a lot more useful than I thought.
A flat battery can cause clocks to speed up
On p110 of the May 2025 issue (in Ask Silicon Chip),
Geoff Graham replied to a correspondent regarding a GPS
Analog Clock gaining time, saying he had not encountered
anything that might cause a clock to speed up when the
battery voltage dropped.
My 40-year-old 1.5V AA cell powered kitchen clock
speeds up when the battery voltage drops. It keeps reasonable time when the battery voltage is 1.5V or higher,
but speeds up when the battery voltage is 1.4V or lower.
That’s how I can tell that it’s time to replace the battery!
As a result, I usually replace the cell twice per year.
SC
John Rajca, Mount Kuring-gai, NSW.
10
Silicon Chip
Australia's electronics magazine
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100mF
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10MHz
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20MΩ
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60MΩ
100μF
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6000µF
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Despite only being
founded in 2002, SpaceX
is now the world’s foremost
provider of space launch
services. SpaceX has been
responsible for dramatically
decreasing the cost of
access to space and is
aiming to land people on
Mars. They’re also behind
the Starlink constellation of
communications satellites.
Part one of two
by Dr David Maddison
VK3DSM
Starship’s
seventh
test
flight
Image source: SpaceX / <at>
Space_Time3 via X (Twitter).
14
Silicon Chip
A size comparison of common rockets from the last few decades. Unlike SpaceX’s,
Australia's electronics magazine
siliconchip.com.au
most are not reusable (exceptions include the Space Shuttle & New Glenn).
Sources: Blue Origin, FloraFallenrose (Wikimedia) & public domain sources
O
f the many achievements of
SpaceX, their ability to vertically land and reuse a rocket is
particularly notable. Never routinely
done before they made it normal, it
has enabled a great decrease in space
launch costs.
Their satellite constellation, Starlink, provides global internet services
at a price not too much different from
regular wired or wireless services.
SpaceX’s Falcon 9 rocket has regular weekly launches (sometimes more
frequent) and is usually reused. It can
carry a larger payload if its boosters are
not reused. It has become a workhorse
of the industry for delivering crew and
cargo into space.
At the time of writing, Falcon 9 rockets have launched 453 times. SpaceX’s
competitors like Arianespace (the
world’s first commercial launch service), Roscosmos (a Russian stateowned corporation) and ULA (United
Launch Alliance, a joint venture of
Lockheed Martin and Boeing) cannot
currently compete with SpaceX on
cost or delivery schedule.
As a result, SpaceX dominates the
launch services market. According to
Space Insider, in the fourth quarter
of 2023, SpaceX launched 382,020kg
of cargo into space, which was 318
times more than ULA. China’s stateowned launch service, CASC delivered, 40,810kg in the same period.
Note that dates provided in this article refer to the local time at the event
location, not Australian time. Also, any
images that are uncredited are publicity images provided by SpaceX or in
the public domain (eg, from NASA).
The objectives of SpaceX
The chief objectives of SpaceX are
stated as:
1. Developing affordable access to space
2. Developing and launching Starlink
for global internet access
3. Sending humans back to the Moon
4. Establishing a colony on Mars
Successes and failures
Like any space agency, SpaceX
has had a few failures, especially
with its early rockets.
Antares Ariane 5
Soyuz
Space
Shuttle
Failure is not treated by SpaceX with
despair, but rather as a learning experience. Failures are to be expected,
after all; they are pushing the limits of
technology and are trying things that
have never been done before. Notable
events in SpaceX history are:
14th of May 2002
SpaceX was founded.
28th of September 2008
SpaceX’s first rocket launch to reach
orbit, the Falcon 1, which was also
the first privately developed liquidfuelled launch vehicle to reach orbit.
8th of December 2010
The first launch, orbit and recovery
of a privately developed spacecraft,
SpaceX’s Dragon.
25th of May 2012
Dragon was the first commercial spacecraft to dock with the International
Space Station (ISS).
3rd of December 201
The SES-8 communications satellite
was launched on a Falcon 9. This
was the first SpaceX mission to place
a spacecraft in a geostationary transfer orbit.
22nd of December 2015
SpaceX achieved the first orbital
rocket propulsive landing.
8th of April 2016
The first propulsive landing on an
autonomous drone ship.
27th of September 2016
SpaceX’s Interplanetary Transport
System was unveiled, comprising the
most powerful rocket ever built, to
carry 100 passengers to Mars with a
view to establishing a self-sustaining
Martian colony by 2050.
30th of March 2017
The first re-flight of an orbital rocket
(Falcon 9 B1021 was
first flown on the 8th of April 2016).
It was recovered after its second flight.
3rd of June 2017
A previously used Dragon spacecraft
was launched to resupply the ISS. This
was the first time Dragon was reused.
It was reused a third time, landing on
the 7th of June 2020.
6th of September 2017
Starship was announced, then known
as Big Falcon Rocket (BFR). It is the
largest rocket seriously conceived.
6th of February 2018
Falcon Heavy was launched into solar
orbit.
24rd of May 2019
The first 60 operational Starlink satellites were launched.
30th of May 2020
The first launch of the Crew Dragon
spacecraft, Demo-2, on a Falcon 9
rocket. The astronauts onboard were
transferred to the ISS. It was the first
crewed orbital flight conducted by the
United States since the cessation of the
Space Shuttle program in 2011.
24th of October 2020
The 100th SpaceX rocket was launched,
carrying Starlink satellites.
16th of November 2020
The first fully operational flight of
Crew Dragon, Crew-1, to the ISS. It
was also the first of the Commercial
Crew Program flights to the ISS under
contract to NASA.
16th of September 2021
The first private fundraising flight on
Crew Dragon by Jared Isaacman, founder
of the Polaris program, on a Falcon 9
rocket. This was also the first orbital
spaceflight with all private citizens.
Known as Inspiration4,
Energia Atlas
Falcon Falcon Delta IV Yenisei New
Long Ares I SLS
New
V Vulcan 9
Heavy Heavy
Glenn March 9
Block 1 Glenn
2-Stage
3-Stage
N1
Ares V
Saturn
V
SLS
Starship
Block 2
Cargo
the flight obtained an orbital altitude
of 585km, the fifth-highest ever orbit
for human spaceflight. The mission
lasted just under three days.
8th of April 2022
The Axiom Ax-1 mission to the ISS
carried four private astronauts, one
a professional astronaut and three
“space tourists” aboard a Crew Dragon
launched by a Falcon 9. This was the
first time private citizens visited the
ISS as tourists, although they conducted some experiments. The tourists
paid US$55 million per seat.
20th of April 2023
The first flight test of Starship atop a
Super Heavy booster as an integrated
assembly. It became the most powerful rocket ever flown. A lot of damage
was done to the launch pad due to
the enormous power of the engines.
Problems were encountered several
minutes into the flight, and the autonomous flight termination system activated to destroy the rocket.
18th of November 2023
The second test flight of Starship. Both
the booster and Starship were lost.
15th of February 2024
A Falcon 9 delivered the first American spacecraft to land on the Moon
since 1972, the Odysseus lander by
Intuitive Machines.
of America due to a loss of comms at
the landing site caused by damage to
an antenna during launch. Starship
performed a controlled splashdown in
the Indian Ocean as planned.
16th of January 2025
The seventh test flight of Starship.
Super Heavy landed successfully but
Starship was destroyed.
2nd of March 2025
Blue Ghost Mission 1 by Firefly Aerospace landed on the Moon. It was the
first fully successful commercial lunar
landing. It was launched on a SpaceX
Falcon 9 rocket.
6th of March 2025
The eighth test of Starship. Super
Heavy landed successfully but Starship
was destroyed. This was the last
Starship launch at the time of writing.
6th of March 2025
The PRIME-1 mission landed on the
Moon, launched using a Falcon 9.
4th of April 2025
The private space mission Fram2
splashed down. This was the first time
astronauts have been in polar orbit.
They were in a Dragon capsule, and
an Australian was on board.
SpaceX’s engines
Among the many reasons for the
success of SpaceX is the innovative
design of its engines and the relatively
low cost of their manufacture due to
simplicity of design and the extensive
use of metal 3D printing to minimise
fabrication cost.
SpaceX currently uses two families of
engine for its boosters: the Merlin and
the Raptor. The Merlin is an ‘open cycle’
engine, while the Raptor is ‘closed
cycle’. SpaceX also uses two other types
of engine for manoeuvring and launch
abort, the Draco and the SuperDraco,
which are hypergolic engines.
Rocket engines contain two propellant components: fuel and oxidiser.
Those like the SpaceX Merlin and Raptor engines require turbopumps (similar to jet engines but pumping liquid
rather than air) to bring the fuel components together in the combustion
chamber (see Fig.1).
Hypergolic engines, also used by
SpaceX, require no turbopumps; the
two fuel components come from pressurised tanks and spontaneously combust when they are brought into contact with each other. They are much
simpler than the engines requiring turbopumps (however, some larger hypergolic engines use turbopumps). The
pressurising medium is usually helium.
14th of March 2024
The third test of Starship. It completed
the second stage burn but broke up
during re-entry. The Super Heavy
booster was destroyed before landing.
6th of June 2024
The fourth test flight of Starship. Both
Starship and Super Heavy successfully
performed re-entry and simulated a
vertical landing over the ocean (with
no recovery tower).
13th of October 2024
The fifth test flight of Starship. The
Super Heavy booster landed successfully, while Starship performed a suborbital flight with a soft water landing
as planned (it was never intended to
be recovered).
19th of November 2024
The sixth test flight of Starship. Super
Heavy was planned to land at Starbase,
but had to land on water in the Gulf
16
Silicon Chip
Fig.1: the Merlin engine is open cycle, while Raptor is closed cycle. Source:
https://woosterphysicists.scotblogs.wooster.edu/2022/01/01/merlin-raptor/
Australia's electronics magazine
siliconchip.com.au
In an open-cycle rocket engine such
as the Merlin (Fig.1, left side), some fuel
and oxidiser are burned to create gas
to run the turbopump and the exhaust
from this process is dumped overboard.
In closed-cycle rocket engines such
as the Raptor (also known as staged
combustion engines), the gases from
driving the turbine are routed into the
combustion chamber, where they contribute to thrust. A closed-cycle engine
is more fuel efficient than an open-cycle engine although its design is more
complex (see the right side of Fig.1).
The Merlin engine
The Merlin engine was used on
the defunct Falcon 1 and the present
Falcon 9 and Falcon Heavy boosters.
These engines run on liquid oxygen
and RP-1 kerosene fuels. The current
versions of the Merlin engine in use
is the 1D+, with nine on the Falcon 9
first stage, and 27 on the Falcon Heavy
first stage, which is essentially three
Falcon 9 boosters joined together.
The second stage of the Falcon 9 and
the Falcon Heavy both use one Merlin
1C vacuum engine, which is optimised
for operation in a vacuum rather than at
sea level, with a larger exhaust nozzle.
The Raptor engine
Fundamental to SpaceX’s desire
for high rates of reusability and
RAPTOR 1
turnaround of rocket engines is the
innovative liquid methane/liquid
oxygen fuelled Raptor engine. This
engine is so innovative that it has
been described as a reinvention of the
rocket engine.
The fuel comprising liquid methane and liquid oxygen is known as
methalox, and it has a higher specific
impulse than RP-1 kerosene and liquid
oxygen. Specific impulse is a measure
of rocket efficiency with units of seconds; it indicates the amount of thrust
generated for each unit of fuel used.
The higher the number, the more efficient the engine.
This means the Raptor can provide
more thrust for the same mass of fuel
as the Merlin. Methane is commonly
available; it is the main constituent of
natural gas.
Methalox also does not leave much
residue in the engines, unlike kerosene. This means the engines don’t
have to be cleaned or rebuilt between
uses. Thus, they are amenable to reuse
and quick turnaround, like aircraft
engines, which can be reused immediately after refuelling.
Although methalox has a lower specific impulse than liquid hydrogen/liquid oxygen, that fuel is difficult and
expensive to use for many reasons. It
was used on the 1960s to early 1970s
Saturn V Moon rocket for the second
RAPTOR 2
Fig.2: 33 Raptor engines power
Super Heavy on the IFT-5 test.
and third stages, and is used in the first
and second stages of NASA’s Space
Launch System (SLS) today.
The Raptor engine is used on the
Starship and Super Heavy booster, for
missions to Earth orbit, the Moon and
eventually, Mars. The Super Heavy
booster has 33 engines; 20 are fixed,
while the inner 13 can be gimballed
for steering (see Fig.2). Starship has
six engines: three regular Raptors and
three vacuum variants. The vacuum-
optimised Raptor variant is named RVac.
The Raptor engine has been in
a development cycle of constant
improvement, simplification and
weight and cost reduction; see Fig.3
RAPTOR 3
Fig.3: the Raptor 3 is the current model of the engine. As the development progressed, they were simplified, yet the
performance increased. Source: https://x.com/SpaceX/status/1819772716339339664/photo/1
siliconchip.com.au
Australia's electronics magazine
July 2025 17
and Table 1. For more details on how
Merlin and Raptor engines work,
see the video at https://youtu.be/
nP9OaYUjvdE
The Draco engine
The Draco engine is a small rocket
thruster used on the Crew Dragon and
Cargo Dragon capsule for manoeuvring
and attitude control. Each Dragon
spacecraft has 16 Dracos. The fuel used
is a hypergolic mixture: monomethyl
hydrazine and nitrogen tetroxide. Each
thruster generates 400N of thrust, or
about 40.7kg-force.
It is comparable to the Marquardt
R-4D thrusters (490N thrust) used on
the Apollo Service and Lunar modules, modernised versions of which
are still in use today (but which use
hydrazine instead of monomethyl
hydrazine). Fig.4 shows a Draco operating as the capsule autonomously
docks with the ISS.
For a video from the same mission of
the Dragon later undocking using the
Draco thrusters, see https://youtube.
com/shorts/AadTz2eqGq4
The SuperDraco engine
The SuperDraco (Fig.6) was originally intended for propulsive landing of the Dragon spacecraft as well as
being part of the Launch Abort System
(LAS), but it was only used on Crew
Dragon for emergency escape during
a launch – see Fig.5.
The Dragons land on water using
parachutes for descent, but in the
Fig.4: Cargo Dragon firing a Draco
thruster (the orange flame) while
docking with the ISS.
Fig.5: a demonstration of the Crew
Dragon launch escape capability
using the SuperDraco engine.
unlikely event of a complete parachute
failure, Crew Dragon can, per a recent
enhancement, be propulsively landed
using the SuperDracos.
There are eight SuperDracos in four
pairs on each Crew Dragon. Cargo
Dragon does not need this safety feature, so it is deleted to save weight.
Each SuperDraco has a thrust of 71kN
(7240kg-force), a burn time of 25s and
a chamber pressure of 6.9MPa (69 bar).
special measures are taken. There is
very little written about how SpaceX
solves this for the Draco thrusters.
Methods that can be used include
keeping the fuel in a bladder with the
outside of the bladder pressurised;
a sliding diaphragm in the tank; the
use of surface tension effects to keep
a quantity of fuel in place near the
tank outlet; a small auxiliary header
tank full of fuel; or a small engine with
pressurised gas for an ‘ullage’ burn to
accelerate the spacecraft and to deposit
the fuel at the tank outlet.
Only a small amount of acceleration
is needed to relocate the fuel, then
pumps or pressurisation will push the
fuel into the engine.
Starting a rocket engine in
weightlessness
Starting or restarting a rocket engine
in the weightlessness of space is difficult, as the fuel in the tanks floats freely
and does not settle at the outlet unless
Fig.6: SuperDraco engines on Crew Dragon for the launch escape system.
18
Silicon Chip
Australia's electronics magazine
Fig.7: a Falcon 9 launch.
siliconchip.com.au
Fig.8:
Falcon 9’s
first stage
landing.
Fig.11: the
Falcon 9
fairing.
Fig.9: the
Falcon 9
interstage.
Source:
Teslarati
Fig.10: a
Falcon
9 rocket
with the
Dragon
capsule,
Trunk
and
crew
access
arm.
We suspect that Draco and
SuperDraco use the bladder method.
Both Starship and Super Heavy use
residual gas in the tanks for attitude
control during descent; Falcon 9 uses
nitrogen gas.
SpaceX’s rockets
SpaceX has three main launch platforms in use: Falcon 9, Falcon Heavy
and Super Heavy.
Falcon 1 was SpaceX’s first rocket.
It made five launches, three being
unsuccessful and one with a commercial payload. It was the first privately
funded rocket to reach orbit. It operated from 2006 to 2009, but SpaceX
decided it was not an economical
proposition and started work on Falcon 9. They then rebooked satellite
launches from Falcon 1 to Falcon 9.
Falcon 9 is SpaceX’s current workhorse rocket for commercial launches
(see Fig.7). It first flew on the 4th of
June 2010. In 2020, it became the
first commercial launch vehicle to
put humans into orbit. It is the most
launched rocket in US history that has
an orbital capability.
Falcon 9’s cost per launch in 2024
was US$69.75 million (about $115
million). The total fuelled mass of the
FT version is 549,054kg (about 549
tonnes) and it is approximately 70m
tall and 3.7m in diameter.
A Falcon 9 rocket comprises the
first stage (booster), interstage, second
stage, payload and fairing.
The first stage or booster stage (Fig.8)
is the most expensive stage, and is usually recovered. If the booster is optionally not recovered, it allows a higher
launch payload, although at greater
expense. The first stage has nine Merlin engines.
The interstage (Fig.9) is a section
connecting the first and second stages.
It contains equipment to separate the
two stages and the
grid fins.
The second stage (Fig.12) contains one
Merlin vacuum engine and is impractical to recover. The payload is contained
within a fairing, which is recovered.
It is 13.1m long and 5.2m in diameter (Fig.11). If Dragon or Crew Dragon
is launched atop a Falcon 9 rocket, no
fairing is necessary (see Fig.10).
The FT version of the rocket can
launch 22,800kg into low Earth orbit
(LEO) if the rocket is expended, or
17,500kg if it is to land. For geosynchronous transfer orbit (GTO), its payload capacity is 8300kg if the rocket is
expended, 5500kg if it lands on a drone
ship, or 3500kg if the rocket returns to
the launch site.
Falcon 9 is certified for human
spaceflight. Its payload deliverable to
Mars is 4020kg. It lands on four legs
when it is recovered, and uses its grid
fins for guidance. When it is not to be
recovered, the legs and grid fins are
deleted to save weight and cost.
A user guide for the Falcon 9 and
Falcon Heavy, intended for mission
planning rather than payload design,
is available at www.spacex.com/media/
falcon-users-guide-2021-09.pdf
Falcon Heavy comprises a strengthened Falcon 9 core with two Falcon
9 first stages attached as boosters on
Table 1 – Raptor engine specifications (sea level variants)
Raptor 1 Raptor 2 Raptor 3
Thrust force
185t
230t
280t
Specific impulse
350s
347s
350s
Engine mass
2080kg
1630kg
1525kg
Engine+accessories mass
3630kg
2875kg
1720kg
Chamber pressure
250bar
300bar
370bar
siliconchip.com.au
Australia's electronics magazine
Fig.12: an illustration
of the Falcon 9’s second
stage separating.
July 2025 19
Fig.13: the
Falcon
Heavy
rocket.
Source:
https://
w.wiki/
DkQg
Fig.14: grid fins are deployed during
re-entry for booster guidance.
Fig.16: the simultaneous landing of
two boosters from a Falcon Heavy.
Fig.15: a Falcon 9 lands on a drone
ship off the coast of the Bahamas.
either side (see Fig.13). The boosters
and the core each have 9 Merlin 1D
engines for a total of 27 engines. The
core carries a standard Falcon 9 second stage, with the payload attached
inside a fairing. It is powered by a
single Merlin 1D engine.
Apart from carrying cargo, Falcon
Heavy was designed to carry humans
into space, and has structural safety
margins 40% above flight loads compared to 25% on other human-rated
rockets. It is capable of taking crewed
missions to the Moon or Mars.
Its propellant is liquid oxygen/RP-1
(a highly refined kerosene). The first
stage burns for 187 seconds and the
second stage for 397 seconds. The first
flight of the Falcon Heavy was on the
6th of February 2018.
Both the boosters and core can be
optionally recovered, but if they are,
the payload is reduced due to the extra
fuel that needs to be carried to power
the engines for the descent stage of
the flight.
The options are to recover boosters
and core, just the boosters or none at
all. Recovering the boosters and core
reduces the cost of the launch.
The rocket is 70m tall, while each
booster and the core has a diameter
of 3.7m for a maximum total width of
12.2m. The mass of the rocket without payload is 1,420,000kg (1420
tonnes). It can carry a payload of
up to 63,800kg into low Earth orbit
when both the core and boosters are
not recovered, or less than 50,000kg
when both the core and boosters are
recovered.
It can carry a payload of 26,700kg
into GTO, 16,800kg to Mars or 3,500kg
to Pluto if the boosters and core are
expended. If the boosters are recovered, the payload to GTO is 16,000kg
and if the core is also recovered, the
payload to GTO is 8,000kg.
The Falcon Heavy has the fourth-
largest payload capacity of any rocket
to ever reach orbit, after NASA’s SLS,
the obsolete Soviet Energia (which
made two flights) and the US Saturn V, which made 13 flights. Thus,
of current rocket systems, it has the
second-highest payload capacity after
the SLS.
Super Heavy is the booster (first
stage) for the Starship spacecraft,
which together are the largest rocket
ever made, with a combined mass
of approximately 5,000,000kg (5000
tonnes) or perhaps more. Both vehicles, Super Heavy and Starship, are
designed to be reusable.
Fig.17: capturing the Super Heavy booster on the 6th of March 2025. Source: SpaceX & Steve Jurvetson
20
Silicon Chip
Australia's electronics magazine
siliconchip.com.au
Fig.18: recovering the payload fairing by parachute.
Fig.19: the Dragon capsule (uc.edu).
The booster is 71m tall. With the 9m
diameter ‘vented interstage”, it has an
empty mass of 275,000kg (275 tonnes)
and a gross mass, when fuelled, of
3,675,000kg (3675 tonnes). It is powered by 33 Raptor engines with a
total thrust of 73,500kN/7,490,000kgforce (Block 1), 80,800kN (Block 2) or
98,100.1kN (Block 3).
Block 1 rockets have a burn time
of 166 seconds and use methalox
propellant.
When Starship separates from
Super Heavy, the Starship engines
ignite while the booster is still
attached, thus ‘pushing off’ from
Super Heavy. This is the reason for
the vented interstage connector; the
‘hot staging’ provides extra thrust. It
was stated that this allows for up to
10% more payload to LEO.
The payload capacity of Super
Heavy into LEO is 100-150 tonnes
when the rocket is recovered. The
payload might be Starship carrying
satellites, up to 100 people going to
Mars, cargo, fuel, passengers to the
Moon or point-to-point transport on
Earth.
For an image of Super Heavy landing and being captured by Mechazilla
(more on that later), see Fig.17.
The Saturn V was the world’s most
powerful, successful rocket until the
Super Heavy came along.
Falcon & Super Heavy
re-entry
When the Falcon 9 or Falcon Heavy
first stage boosters perform re-entry,
the engines first slow the booster(s),
then the grid fins (Fig.14) help to orientate and guide the booster(s) for a
landing on either a drone ship (see
Fig.15) or the landing zone on land
LZ1 or LZ2 (Fig.16).
A landing of Falcon or the side
boosters of a Falcon Heavy usually
occurs at LZ1 and LZ2, while the core
booster lands on a drone ship if it is
a full recovery mission. The fairing
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used to protect the payload is also
recovered by parachute and reused
where possible (see Fig.18).
The second stage is not recovered because it is travelling too fast
(27,000km/h) and would require
too much fuel to slow down and re-
enter, unlike the first stage, which is
moving much slower. The first stage
would eventually fall back to Earth
in any case.
Grid fins
On Falcon 9, Falcon Heavy and
Super Heavy, grid fins are used and
guide the booster to a landing (Fig.14).
For Super Heavy, the landing is in the
“Mechazilla” structure. The boosters
have four grid fins each. Those on Falcon 9 and Falcon Heavy are made of
titanium and measure 2 × 1.2m. They
are folded during ascent.
On Super Heavy, they remain
extended to simplify the design and
save weight. In this case, each measures 7 × 3m, is made of stainless steel
and weighs three tonnes. When the
boosters re-enter, they return enginefirst; the heat-resistant engines act as
a de facto heat shield.
Super Heavy vs the N1 and
Saturn V
On the 20th of April 2023, the Super
Heavy rocket broke the record for the
most powerful rocket. For the 50 years
before that, the record was held by the
Soviet N1, a competitor to the United
States’ Saturn V Moon rocket. However, the N1 never achieved orbit after
four attempts.
Similar to Super Heavy with 33
engines generating 73,500kN of
thrust, the N1 had 30 engines and
produced 45,400kN of thrust. The
US Saturn V with five engines generated 34,500kN of thrust and successfully took astronauts to the Moon.
Australia's electronics magazine
Spacecraft
SpaceX’s main spacecraft in use or
under development now are variants
of Dragon and Starship. The Dragon
spacecraft are primarily designed for
crew and cargo transport to the ISS
and Earth orbit. Starship is designed
for heavy lifting of crew, cargo and
fuel to locations on the Earth’s surface, Earth orbit, the Moon, Mars and
elsewhere.
Starhopper was a test vehicle built
for the purpose of landing and control
algorithms for Starship and flown four
times in 2019. It used methalox fuel.
Dragon 1 flew 23 cargo missions
to the ISS from 2010 to 2020. It was
not designed to carry astronauts and
was the first private spacecraft to dock
with the ISS.
Dragon 2 (Fig.19) was introduced
in 2019, with both Crew Dragon and
Cargo Dragon variants. The Crew
Dragon carries astronauts to and from
the ISS under NASA’s Commercial
Resupply Services (CRS) program and
also on orbital missions such as the
recent Fram2 (Fig.20).
Fig.20: recovery of the Fram2
mission Crew Dragon capsule. Note
the scorch marks from re-entry.
July 2025 21
Fig.21: note how (relatively) spacious the interior of the Crew
Dragon capsule is. These are the SpaceX Crew-8 astronauts.
The Crew Dragon usually carries
four astronauts, but it can be configured to carry seven. The interior is
relatively spacious (see Fig.21). Both
types of Dragon spacecraft are fully
autonomous, but astronauts or Mission Control can take control of Crew
Dragon if necessary. Like Dragon 1,
Dragon 2s (which are now called Crew
Dragon or Cargo Dragon) are reusable.
Also see Figs.22, 23 & 24.
The Dragon 2 capsules are 8.1m
tall, 4m in diameter, with a volume of 9.3m3 and a launch mass of
6,000kg (six tonnes). The return mass
is 3,000kg (three tonnes).
For landing, Dragon is designed to
re-enter the Earth’s atmosphere, where
it is initially slowed by its heat shield.
Drogue parachutes are then released,
Fig.22: The Trunk section at the back of the Dragon 2
capsule is discarded after launch.
followed by four main parachutes.
Crew Dragon can land safely even if
only one of the four parachutes deploy
(see https://youtu.be/YDFgFnEVn_o).
After landing in the ocean, the main
parachutes are disconnected to stop
the capsule being dragged by the wind.
The capsule is designed to float by
itself, but if necessary, extra flotation
devices can be deployed in an emergency to prevent the capsule sinking.
The Dragon capsules were originally
intended to land propulsively using
SuperDraco engines, but this idea was
abandoned in favour of ocean splashdowns. The Crew Dragon also has
SuperDraco engines in case of a launch
failure, to remove the capsule from the
rocket and move it to safety for a parachute landing (shown earlier in Fig.5).
The Cargo Dragon does not need this
safety feature, so it does not have the
SuperDraco engines installed.
In the unlikely event of a total
parachute failure, Crew Dragon now
has the ability to use the SuperDraco
engines to land propulsively. The reason the original plans for Crew Dragon
to land propulsively were abandoned
was partly due to NASA’s requirement
for a parachute landing on water. But
now propulsive landing has been reinstated as an emergency measure.
The Dragon carries a Trunk module with a 37m3 volume, which is
unpressurised and can carry cargo. It
is half-covered in solar panels to generate power for the capsule while in flight
or docked at the ISS. The other half is
covered with a thermal radiator system.
Active Vent Valves
Emergency
Ventilation Fan
Dehumidifier Vacuum
Isolation Valves
Fig.23: a cutaway of
Dragon capsule, from the
same source as Fig.24.
Toilet
Dehumidifier
Vacuum Lines
Fire Extinguisher
Valve Panel
Cabin Fans
Dehumidifier
Waste Locker
Active LiOH
Cartridge
Valve Panel
Waste Fans
Urine Tank
Fig.24: some of Dragon’s plumbing and thermal
controls. Source: www.uc.edu/content/dam/
refresh/cont-ed-62/olli/fall-23-class-handouts/
SpaceX%205Dragon%20Capsules.pdf
22
Silicon Chip
Australia's electronics magazine
siliconchip.com.au
Fig.26: a rendering of the USDV designed for deorbiting
the ISS. It is a modified Dragon. Source: https://x.com/
SpaceX/status/1813632705281818671/photo/1
Fig.25: under the skin of the Dragon capsule (uc.edu).
The Trunk module is jettisoned
before re-entry and is meant to burn up
in the atmosphere, but parts of it occasionally survive re-entry. The Trunk
provides the mechanical and electrical interface to the Falcon 9. The Trunk
also has fins to stabilise the Dragon and
Trunk in the event of an aborted launch.
Electrical and fluid connections are
provided inside the trunk to accommodate various payloads, including
small satellites. The Trunk space is
almost ‘free’ and represents the utilisation of an area that would otherwise
be unused.
Fig.25 shows the inner structure of
the Dragon, which is made of aluminium, while the outer shell is carbon
fibre. Section A is the pressure vessel, which contains the crew couches,
while section B contains equipment.
The primary heat shield at the bottom is
made from PICA-X (more on that later).
Dragon 2 communicates by several
methods. It connects to satellites via
NASA’s Tracking and Data Relay Satellite System; it can communicate with
ground stations with a 300kbps Command Uplink and 300Mbps+ telemetry
and data downlink. Payloads can be
connected to the vehicle via Ethernet,
RS-422 and MIL-STD-1553.
There are redundant communications systems via telemetry and
video transmitters on S-Band and, as
of Fram2, connectivity with Starlink
via laser.
There was once a Red Dragon proposal to propulsively land an uncrewed
Dragon capsule on Mars to deliver
equipment and a sample return rover.
Propulsive landing would be ideal
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on Mars since the thin atmosphere
makes parachute landings difficult. Red
Dragon was abandoned when Starship
became the focus for trips to Mars.
Dragon XL is a planned variant that
will be used to supply NASA’s Lunar
Gateway, a planned space station in
lunar orbit. It will carry cargo and
experiments, keeping up to 5,000kg
(five tonnes) of supplies in lunar orbit
with the Gateway for 6–12 months.
The XL is not required to return to
Earth; after use, it will be parked in a
heliocentric orbit (ie, orbiting the sun).
When the ISS is finally deorbited, as
planned in the early 2030s, a modified
Dragon called the US Deorbit Vehicle
(USDV; Fig.26) will dock with the ISS
and use 46 Draco engines attached to
a larger-than-usual trunk section to
guide and push it into the atmosphere
at an appropriate place.
This will ensure that the structure
burns up over the Pacific Ocean and
any small remaining debris will fall
into the empty ocean after shipping
has been cleared from the area. The
USDV will have six times the propellant and four times the power of a
regular Dragon. It will be a sad ending
for the ISS but is necessary for reasons
explained in the video at https://youtu.
be/cohVHaVMBl8
Starship
Starship and its variants (Fig.27)
will be a highly versatile workhorse
of the future SpaceX fleet, delivering
Fig.27: Starship ready for launch. One of the thermal protection tiles has
been removed for testing purposes.
Australia's electronics magazine
July 2025 23
people, cargo and fuel to other locations anywhere on Earth in less than
one hour or into Earth orbit, the Moon,
Mars and beyond.
Starship is the second stage of the
Super Heavy booster. Perhaps confusingly, the ‘stacked’ (combined) Super
Heavy booster and Starship second
stage might also be called Starship
together.
The depot version of Starship
will remain in orbit and so does not
require heat shields or control surfaces. The HLS version, which will
shuttle between Earth and Moon and
will not land on Earth, is similar. Propellant tankers, which can land, can
also refuel other Starships.
When stacked with Super Heavy
and fuelled (Fig.28), Starship has
a total mass of approximately 4975
tonnes (Block 1) or 5260 tonnes (Block
2) and a height of 121–123m depending on the version. It is the largest
and most powerful rocket ever built
and the heaviest object ever flown.
Starship can deliver 100–150 tonnes
of cargo if reused, or 250 tonnes if the
booster is expended.
Versions of Starship for landing
on the Moon or Mars will have landing legs.
One possible use of Starship is for
rapid delivery of supplies for military
missions or natural disasters on Earth.
It will be able to reach anywhere on
Earth within one hour.
For landing on Earth, Starship will
use four flaps for guidance, two forward and two aft, as well as grid fins. It
will be caught in the arms of a Mechazilla structure, like Super Heavy. Heat
shields protect it during re-entry.
The Starship second stage has
a height of about 50m (Block 1) or
52m (Block 2), a diameter of 9m, an
empty mass of about 85,000kg (85
tonnes) and a fully fuelled mass of
1,500,000kg (1500 tonnes). Starship
uses methalox fuel, with three Raptor engines and three Raptor vacuum
engines.
The versions of Starship optimised
for lunar landing will have legs, and
possibly engines that are mounted
higher up, to avoid kicking up lunar
dust. Such versions will shuttle
between the Moon and Earth orbit,
where they will be refuelled and will
not land on Earth. It is estimated
that eight Starship launches will be
required to get enough fuel into orbit
for one refuelling.
Why use so many engines?
Compared with the Space Shuttle,
the Saturn V and other rockets that
use relatively few engines, SpaceX
rockets use many (see Fig.29). This
Fig.28: Starship & Super Heavy
booster for Starship’s 8th flight test.
24
Silicon Chip
relates to propulsive landing. Large
rocket engines have a limited range of
thrust in which they will work, and
cannot be throttled back to the relatively low thrust levels required for
a landing (other rocket designs can’t
land this way).
Note that while all engines are used
for launch, only some are reignited
for landing.
Smaller engines that can work
within the required thrust range are
needed. However, because their thrust
is relatively low compared to large
engines, more are needed for launches.
Having many engines also makes the
failure of one more tolerable.
Another advantage is that standardising on a few engine designs for multiple rocket designs enables greater
economies of scale of mass production. SpaceX wants to have a fleet of
hundreds or thousands of rockets running continuous missions into Earth
orbit and beyond.
Next month
There is more to this story, but
that’s all we can fit in this issue. In
the second and final part next month,
we will have details of SpaceX’s proposed Mars missions using Starship,
more on the rocket recovery methods,
their launch sites and some notable
missions SpaceX has undertaken.
We’ll also have some brief updates
on two of their main competitors,
Blue Origin and Virgin Galactic. Along
with SpaceX, they were both mentioned in our October 2018 article
on Reusable Rockets (siliconchip.au/
Article/11257), but much has changed
since then.
Fig.29: Falcon 9 has nine engines in its first stage, Falcon Heavy has 27,
while Starship has 33! This gives redundancy and better control for landing.
Australia's electronics magazine
siliconchip.com.au
Elon Musk: a controversial figure
Elon has been somewhat divisive since he became one
of the world’s richest people. These days, “controversial”
is putting it mildly! Still, as the founder of and visionary
behind SpaceX, we can’t tell the story of the company
without mentioning him.
Whether you love him, hate him, or are totally indifferent, he
has been a driving force behind several major technology
companies, including PayPal, SpaceX, Twitter/X, OpenAI and
Neuralink, among others.
Elon Musk’s engineering philosophy
These are the distinguishing characteristics of his businesses, as opposed to traditional, more conservatively run
ones. He emphasises excellence, high-quality engineering
and simplicity of design, as quoted in Walter Isaacson’s
biography of Musk:
A humourous AI-generated image of Elon Musk and
Optimus with Starship on Mars (one wonders how he
is breathing with his helmet removed).
1) Question every requirement. Each should come with the name of the person who made it. You should never accept that
a requirement came from a department, such as from “the legal department” or “the safety department.” You need to know
the name of the real person who made that requirement. Then you should question it, no matter how smart that person is.
Requirements from smart people are the most dangerous, because people are less likely to question them. Always do so,
even if the requirement came from me. Then make the requirements less dumb.
2) Delete any part or process you can. You may have to add them back later. In fact, if you do not end up adding back at
least 10% of them, then you didn’t delete enough.
3) Simplify and optimize. This should come after step two. Common mistake is to simplify and optimize a part or a process
that should not exist.
4) Accelerate cycle time. Every process can be speeded up. But only do this after you have followed the first three steps.
In the Tesla factory, I mistakenly spent a lot of time accelerating processes that I later realized should have been deleted.
5) Automate. That comes last. The big mistake in Nevada and at Fremont was that I began by trying to automate every step. We
should have waited until all the requirements had been questioned, parts and processes deleted, and the bugs were shaken out.
Elon is quoted as saying, “the best part is no part”. Another aspect of Musk’s philosophy is that he sees patents as
“stifling” and, in 2019, he made Tesla’s entire patent portfolio available under Creative Commons licensing for non-
commercial purposes. With regards to SpaceX, he said, “If things are not failing you’re not innovating enough.”
He wants to see rocket launches become as routine as airline flights, and nearly as cheap, with a similar turnaround time
between flights. He wants to ‘democratise space’ and making it accessible to
as many people as possible.
Musk has said that with SpaceX, he spends more time on government paperwork than rocket development.
On the 15th of March 2025, Elon Musk announced on X that “Starship departs
for Mars at the end of next year, carrying Optimus. If those landings go well,
then human landings may start as soon as 2029, although 2031 is more likely.”
(https://x.com/elonmusk/status/1900774290682683612). Optimus is the
humanoid robot designed by Tesla.
As for the continuing development of Starlink, Elon Musk Tweeted on the 15th
of October 2024 that, “The next generation Starlink satellites, which are so
big that only Starship can launch them, will allow for a 10X increase in bandwidth and, with the reduced altitude, faster latency” (https://x.com/elonmusk/
status/1845884681050276333).
SC
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Australia's electronics magazine
The current Starlink constellation.
Source: satellitemap.space
July 2025 25
USB Solar Charging
System
Simple Electronic Projects with Julian Edgar
Charge and power all your USB devices from solar with this low-cost system. It’s inexpensive to put
together, and once you’ve built it, charging your devices won’t cost a cent!
I
have lots of solar-powered devices.
A solar-powered smart watch, a
solar-powered iPhone, solar-powered
noise-reducing headphones and a
solar-powered mini floodlight. In fact,
every one of my devices charged from
a USB adaptor is now solar powered.
This is achieved very simply and, if
you’re careful with your purchasing,
very inexpensively too.
The parts required
Only a few parts are required: a solar
panel (Photo 1), a charge controller
(Photo 5), a 12V battery and a one or
more 12V to 5V USB converters (Photos 2, 3 & 4). You could spend hundreds of dollars on assembling these
parts – or you could do as I did, and
buy mostly second-hand, via online
market places and/or make use of parts
that others have thrown away.
The solar panel needs to have an
output voltage suitable for charging a
12V battery through a charge controller. This means getting a panel that
has a maximum open circuit voltage
of about 18-30V, depending on the
selected controller.
The maximum solar panel output
power will also be governed largely by
the controller you select. Small charge
controllers may have a 60W limit,
while larger controllers are good for
250W. So selecting the correct panel
is done in conjunction with the charge
controller you’ve picked.
Second-hand solar panels are now
ridiculously cheap – expect to pay
from about $25 for a suitable used
panel. Also remember that, in this
application, the panel’s original maximum output power is probably not
needed. To put that another way, this
is a good project for reusing degraded
panels that otherwise would go to
scrap.
The appropriate charge controller
Photo 1: I mounted this 100W solar panel on a disused satellite dish on the
roof. The panel can also be wall-mounted, or even just anchored to the ground.
Second-hand solar panels are now very cheap.
26
Silicon Chip
Australia's electronics magazine
will also depend on the battery type
you’re going to use. Sealed lead acid
(SLA) batteries are ideal for this application as they can be mounted inside
without concern for acid spills or venting of gases. However, SLA batteries
tend to be expensive – even second-
hand – so you may wish to use a conventional car battery.
A major benefit of using a car battery
is that you can get one free of charge.
Simply visit a local mechanic or car
battery supply shop. There you will
find literally dozens of batteries that
have been discarded – they’ve been
replaced as no longer being suitable
for cranking engines.
However, starting an engine is very
demanding on a battery; the current
draw is in hundreds of amps. So these
batteries often still have sufficient
capacity to work as a storage battery
in a solar system of the type being
covered here.
Photo 2: this 12V-to-USB converter/
charger provides two outputs and a
voltmeter to allowing monitoring of
system voltage. It cost about $11 from
Banggood (similar units can be found
on AliExpress & eBay).
siliconchip.com.au
Solar panel and battery ratings
The greater the power of the solar panel, the better it will work through poor
weather and the more battery charge you will have to work with. Also, the
larger the battery, the longer the system will cope with cloudy days when little
solar output is available.
To give you a guide, where I live about 100km north of Canberra, in four
years I have never gone close to running out of power using a 100W panel and
a 26Ah SLA battery – the latter bought as defective and so probably having
only half this nominal capacity. That includes charging power tool batteries
as well as my phone, watch, camera, etc.
Note also that smaller panels and batteries tend to be more expensive
second-hand, so there’s a further advantage in going big.
When selecting a battery from the
discard pile, use a multimeter to find
a battery that still has an open-circuit
voltage above 12V. If you are going to
use the battery inside, select one that
is fully sealed.
A battery with flat terminals to
which lugs can be bolted will be easier to wire than a battery with round
terminal posts. If you have one with
round posts, you’ll need to get matching terminals to attach wires to it (eg,
Jaycar Cat HC4038), which will be an
extra cost.
Once you have selected a solar
panel and battery, you can pick a
charge controller to suit. Here it’s
worthwhile buying new. At the time
of writing, a 30A (about 400W) 12V
charge controller costs around $12,
including freight. They can be bought
from AliExpress and similar suppliers. Ensure the controller can be configured to suit the battery type you’re
using – most can.
Many controllers also have built-in
USB 5V outputs. If you choose to use
these, you don’t need to buy an additional USB converter. However, more
for convenience and appearance, I
added three USB output converters
to my system. Each of these has two
USB outputs (giving six in total), on/off
switches and an onboard LED display
showing the battery voltage. These
units are about $11 each.
Note that when selecting these,
ensure you don’t get ones designed
to plug into a cigarette lighter socket
– you want wired-in ones.
If you want an even cheaper
approach, just buy a 12V-to-USB wired
converter that comprises a sealed box,
USB output socket on a lead, and input
power connections.
In addition to these parts, you will
need assorted cabling, terminals,
an inline fuse holder and fuse, and
siliconchip.com.au
possibly a panel on which to mount
the USB outlets.
Building the system
Before starting to build the system,
consider the cabling requirements.
I have the charging system working
in my home office, so I had to run
a cable from the roof-mounted solar
panel through the wall of my house.
In my case, that was easy but, in many
houses, that will be quite hard! If that’s
Photo 3: this non-switched panel with
two USB outputs costs about $6 from
AliExpress. Ensure you get a device
that runs from 12V.
the situation, consider having the
charging system in an outside workshop or shed.
It will still be very useful there – for
example, most battery-powered tools
have 12V car chargers available for
their batteries, so the system can be
used to charge power tool batteries.
Also, consider how the solar panel
will be mounted. In my situation, a
disused satellite TV dish antenna was
on the roof, pointing north. Mounting
Photo 4: in my system,
three 12V-to-USB adaptors
provide six outlets at the
desk in my home office.
Note the inconsistency in
the voltage readouts – at
these prices, you can’t
expect perfection! This is
the charging voltage on a
sunny day.
Photo 5: this solar panel
charge controller from
AliExpress incorporates
two USB outputs so, if
you wish, you can charge your
items directly from this module.
Australia's electronics magazine
July 2025 27
the panel was just a case of attaching the panel to the dish – quick and
easy! However, again, that may not
be the situation in your case. If roof-
mounting is difficult, consider mounting the panel on a wall or even on the
ground.
The panel should face north and be
tilted at an angle that approximately
corresponds to your latitude, although
horizontal panels will generally work
OK. We don’t need to squeeze every
drop of power out if it!
Fig.1 shows the wiring – it is very
simple. Ensure you place the fuse
close to the battery; it should be rated
at the maximum charging current, as
dictated by the controller.
If you are not used to working with
12V storage batteries, keep in mind
that although the voltage is low (so you
won’t get a shock), the ability to deliver
current is very high and so you must
be careful to ensure that the battery is
never short-circuited. I have seen this
done when someone inadvertently
dropped a spanner across the battery
terminals... not good!
Always take great care when attaching battery connectors; the battery terminals must be insulated when the battery is in use. An easy way to achieve
this is to place the battery in a dedicated box. Boxes designed to house
car batteries are available from about
$15 from local suppliers.
First, connect the battery to the solar
Parts List – USB Solar Charging System
1 12V solar panel
1 12V charge controller (type to suit panel and battery)
1 12V rechargeable battery
1 pair of battery terminals (may not be required depending on battery type)
1 inline fuse, rated to suit charge controller
1 or more 12V-powered USB chargers
various lengths of wire, rated to handle the maximum charging current
Fig.1: the wiring is straightforward,
but ensure you maintain the correct
polarity of all the connections. Don’t
insert the fuse until you have wired
the battery to the controller.
controller, ensuring the polarity of the
connections is correct. Once these
connections are made and insulated,
insert the inline fuse. The controller
should then come alive.
Set the controller to the correct
battery type, and if the controller has
these facilities, ensure the settings for
float charge and auto-disconnect (that
occurs if the battery is discharged
too far) are correct – many simpler
charge controllers won’t have these
functions.
Next, connect the solar panel to
the controller, again ensuring correct
polarity of the wiring. If you’re unsure
of which wire is which (an easy confusion to occur if you’ve extended the
solar panel wiring), use a multimeter
to identify the positive and negative
wires – the solar panel will need to
be exposed to light when you perform
this check.
After the solar panel is connected,
most controllers will confirm the panel
is generating power, either on the LCD
screen or by the simple illumination
of an onboard LED.
Finally, if you are not using a
built-in USB outlet, connect the external USB converter(s). Ensure that no
timers are activated on the controller
output – you want the output on all
the time.
Conclusion
Photo 6: a used car battery that is no longer strong enough to crank a car engine
will often be suitable for this application. Such batteries are available free of
charge from car workshops and battery replacement shops. However, it’s best
to get a battery with bolt-on terminals rather than round battery posts like this
one. If mounting the battery inside, ensure it is of a sealed design.
28
Silicon Chip
Australia's electronics magazine
What has surprised me over the
four years that I have been running
the system is its ease of use and convenience. I just plug in the devices,
and they charge – obvious, huh? But
they charge purely on solar power, and
they charge irrespective of the weather.
Also, they charge through blackouts,
so there’s that safety advantage to conSC
sider as well.
siliconchip.com.au
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B 0007
SmartProbe
Project by Andrew Levido
The SmartProbe is an extremely handy little device for making voltage & continuity
measurements. It won’t replace your multimeter, but it is designed to be the first piece of test
equipment you reach for when debugging or repairing a circuit.
I
have made the SmartProbe very small,
measuring just 60mm long, 30mm
wide and 15mm thick. That’s about
the size of a box of matches, for anyone
old enough to remember one! A probe
fine enough for modern surface-mount
circuits (or through-hole parts) is fitted
to one end of the case, while a short
flying ground lead emerges from the
other.
It is equipped with a 128 × 64 pixel
OLED display and an audio transducer
to show voltage measurements and
give feedback, respectively.
There are no buttons or switches.
The SmartProbe switches itself on
when you pick it up, and off again
when it senses no movement for a few
seconds. You switch between voltage
measurement and continuity modes
by tapping it with your index finger.
The display automatically flips rightway-up however you hold it.
The unit is powered by a single
CR2032 coin cell that should last many
months with typical use.
±0.5%, and the input impedance is
around 1MW on both ranges.
In the continuity mode, the SmartProbe sources a low current (around
1mA) and displays the voltage drop
seen across the probes, just as your
multimeter does on the diode test
range. The source voltage is 3.3V,
enough to forward-bias typical diodes,
transistor junctions and most LEDs.
If the resistance between the probes
is greater than about 60kW, the display
shows “OPEN”. There is an audio indication of continuity if the measured
drop is less than about 1V. The continuity beep responds within a few
milliseconds, which is essential for a
good user experience.
The SmartProbe is not suitable
for use with high-voltage or mains-
owered circuits. While it has a degree
p
of input protection, it does not have
the insulation or overload ratings of
a good multimeter. I considered adding AC voltage or frequency measurement capabilities, but elected to keep
it really small & simple.
Ultra-low power design
The SmartProbe operates in either
voltage measurement or continuity
mode. In the former, it can measure
voltages up to ±50V, switching automatically between two ranges. For
input voltages below ±6V, it has a resolution of 5mV or better; for higher
voltages, the resolution is 50mV.
Its absolute accuracy is within
» Compact size (60 × 30 × 15mm)
and lightweight (24g)
» Measures voltage or continuity
» 128×64 pixel OLED screen
» Internal buzzer for continuity
checking
» Measures up to ±50V
» Can also test diodes/LEDs and
measure forward voltage
» Single fine-tipped probe with a
ground clip
» Powered by an internal CR2032
coin cell
One of the main aims and challenges
of this design was to keep the power
consumption when the device is ‘off’
to a level that would give meaningful battery life, while still being able
to sense movement and wake up. A
CR2032 cell has a capacity of about
235mAh while discharging from 3V
(fully charged) to an end voltage of 2V.
I set myself the goal of aiming for
a shelf life of one year (8760 hours),
meaning less than 27µA of idle consumption. As we shall soon see, that
goal was more than met.
Before diving into the circuit, it is
helpful to look at the block diagram of
the front end (Fig.1). This shows the
device in voltage measurement mode,
with just one voltage range for simplicity. We want to convert a bipolar voltage up to ±50V, appearing between the
probe and clip, to a unipolar voltage
between 0V and 3.3V (V1) suitable for
the analog-to-digital converter (ADC).
We do this by fixing the bottom
(ground clip) end of the Ra/Rb voltage divider to half the supply rail, ie,
around 1.65V. Voltage V1 is therefore
siliconchip.com.au
Australia's electronics magazine
July 2025 33
Specifications
Features & Specifications
Fig.1: one end of the input voltage divider is fixed to ½ of the supply voltage
to provide an offset so that bipolar (±) input voltages can be measured with a
unipolar ADC. The offset is later subtracted by the firmware.
an attenuated and buffered version of
the input voltage offset by ½Vcc, as
described by the equation V1 = (Vin ×
Rb) ÷ (Ra + Rb) + Voffset.
If we also buffer and convert the
offset voltage, Voffset, we can subtract it from the converted version of
V1 in firmware. The resulting digital
code will be a signed value proportional to Vin.
The full circuit (Fig.2) shows that
there are actually two dividers and
associated buffers in the SmartProbe, one for each input voltage
range. For the high-voltage range,
it uses a 2MW/51kW divider, while
the 2MW/680kW divider is for the
low-voltage range. The output of each
is buffered by IC1d and IC1c, respectively, and fed to its own ADC input
channel on microcontroller IC2.
I chose the divider resistor values
such that the voltage span seen by
the ADC inputs is around 3V centred
on around 1.65V (0.15V to 3.15V).
This allowed me to stay away from
the very ends of the ADC range and
avoid a potential source of errors. I
am using ±0.1% tolerance resistors
here, as these are critical to achieving
the required resolution and accuracy.
The op amps are low-cost zerodrift (auto-zero) op amps. These have
a worst case offset voltage of ±10µV
with just 50nV/°C drift. Since they are
connected as unity-gain buffers, there
is no appreciable gain error.
The offset voltage is also buffered
(by IC1a) and fed to another ADC channel. All three of these input buffers are
identical, including protection diode
pairs (D1 through D3), and a small
amount of low-pass filtering on the
inputs (using 1nF/100nF capacitors)
and outputs (1.5kW/1nF). Most of the
filtering of these signals occurs in software, as discussed below.
34
Silicon Chip
When the input voltage is outside the ±6V range, the output of the
low-voltage sensing circuit (IC1c)
saturates, and the digital code associated with this input moves outside
the expected range. The firmware
automatically switches to using the
high-voltage input in this case. If the
high-voltage input approaches saturation, a voltage over-range warning
message is displayed.
The bottom ends of the dividers
are fed by a current-limited buffer,
IC1b. The 10W resistor provides a bit
of protection to the op amp, since its
output would otherwise be connected
directly to the ground clip and therefore exposed to the outside world. The
input of the buffer is connected to a
100kW/100kW voltage divider fed from
one of the microcontroller’s GPIO pins
(PA06, pin 12).
This pin is configured as a digital
output. If it is high, the buffer input is
half of the supply voltage, as in Fig.1.
If the output is low, the bottom end of
the divider is effectively connected to
0V – a state which comes in handy for
continuity mode.
Continuity measurement
So far, we have ignored the network
consisting of Mosfets Q1-Q3 and the
associated passive components. These
form an analog switch that is off in
voltage mode.
In continuity mode, the offset at
the bottom of the voltage dividers is
set to zero, as mentioned above, and
the analog switch is on. This connects
the 3.3V supply to the input probe via
the 3kW resistor. A voltage of approximately 3.3V is therefore present across
the probes when they are open circuit.
This voltage drops as the impedance
between the probe falls, ultimately
to zero if the probe is shorted to the
Australia's electronics magazine
clip. If a diode junction is connected
across the input, with its anode to the
probe, the forward drop of the diode
will appear across the input.
In continuity mode, the voltage is
read by the ADC in the same way as
already described, except the offset
voltage will be close to zero. The equation shown in Fig.1 will still hold, but
we will no longer be able to read negative voltages; that doesn’t matter in
continuity test mode.
You will notice that the output of
buffer IC1c connects directly to the
PA03 pin of the microcontroller, as
well as to the ADC input via the RC
filter. PA03 is internally connected to
a fast comparator that drives the continuity beep tone.
The analog switch
The analog switch deserves a closer
look. We require a switch with a very
high impedance when off, so that no
appreciable current flows through the
3kW resistor when measuring voltages. The switch must withstand ±50V
when open, but have relatively low
on-resistance when closed.
I could not find a suitable off-theshelf analog switch because the voltage requirements are relatively high,
so I built my own using two P-channel
Mosfets with an N-channel Mosfet to
drive them.
The switch is open when Q3 is off,
and the gates of Q1 & Q2 are held at
their source potential by the 100kW
resistor. Since the gate-source voltage
is zero, both Mosfets will be off. You
can see what happens when an external voltage is applied by referring to
the left and middle diagrams in Fig.3.
If the drain of Q1 is at +50V, its
source will also be at this potential
due to the conduction of its body
diode. Both Mosfet’s gates and sources
will therefore be at +50V, so they will
remain off. Q2 will therefore block any
current flow, since its body diode is
reverse-biased.
If the drain of Q1 is at -50V, the body
diode of Q2 is forward-biased, leaving
the sources and gates of both Mosfets at
3.3V. Q1 now blocks any current flow.
When Q3 is switched on, the gates
of both Mosfets gates will be at 0V. The
drain of Q2 is fixed at 3.3V, so the body
diode initially conducts, causing the
sources of both Mosfets to rise almost
to this value. The resulting -3.3V gatesource potential is enough to switch
both Mosfets on, effectively shorting
siliconchip.com.au
Fig.2: the SmartProbe circuit is fairly straightforward, except for a few tricks
related to achieving ultra-low power consumption that are detailed in the text.
out their respective body diodes and
switching the analog switch fully on.
The ZXMP6A17E6 Mosfets I chose
have a maximum Vds of -60V and an
Rds(on) of less than 0.5W with a Vgs
of 2.5V (interestingly, they have six
pins, but the three additional ones
are just extra drain connections).
The total on-resistance of the analog
switch will therefore be around 1W.
The P-channel Mosfets see a worstcase voltage of -53.3V.
siliconchip.com.au
The BSS138K (Q3), with a maximum Vds of 50V, places the upper limit
on switch voltage. This is a bit of a soft
limit, since the 100kW resistor limits
the avalanche current if Q3 were to
break down. Nevertheless, this switch
is what limits the nominal maximum
voltage for the SmartProbe.
Digital circuity
The microcontroller is a 32-bit
STM32L031F6 low-power Arm Cortex
Australia's electronics magazine
M0+ from ST Microelectronics. This
has 32kiB of flash, 8kiB of RAM and
comes in a 20-pin TSSOP package.
Importantly, it operates at any voltage
between 1.8V and 3.6V, and can be put
into various low-power modes where
its current draw reduces to single-digit
microamp levels while still retaining
RAM contents.
The display connects to the microcontroller via an I2C interface. This is a
128 × 64 pixel white OLED screen that
July 2025 35
Both sides of the SmartProbe PCB. The flat flex cable on the back of the OLED is
soldered to the PCB and the screen is then held down with double-sided tape.
measures just 34 × 22 × 1.5mm. These
displays are readily available for just
a few dollars each from AliExpress.
They have a SH1106 control chip
onboard, and can be controlled via
an 8-bit parallel or SPI/I2C serial bus.
The display only needs four 100nF
capacitors and one resistor added to
create the necessary internal voltages
(all shown to the right of DISP1).
The OLED current is set by the resistor. I have used 510kW, which gives a
current of about 10µA per pixel. This
is nice and bright, but means that the
display could draw as much as 82mA
(128 × 64 × 10µA) if all pixels were on.
In reality, the measured current stays
under 20mA or so, since we never
light more than about 25% of the pixels simultaneously.
Nevertheless, the display is the
main current consumer in the circuit
and has to be completely shut down
when the SmartProbe is inactive. To
help ensure it comes up reliably when
awakened, I have wired its hardware
reset pin to a microcontroller GPIO
pin (PC15).
The audio transducer, MB1, is a
small magnetic beeper that requires an
AC signal to operate. This means it can
deliver a variety of tones if driven at
different frequencies. I have used one
of the micro’s PWM outputs (routed to
the PA05 pin) to drive it via Mosfet Q4.
Using a PWM output allows me to
set the tone by varying the PWM carrier
frequency and manage the volume,
and more critically, the current consumption, by limiting the duty cycle.
Even so, it presents a significant (relatively speaking) load on the supply.
For this reason, I used it only when I
think it is really necessary.
Accelerometer
Because the accelerometer is the
only component in this circuit that is
always operational, I needed to choose
it carefully. I selected the LIS2DW12
three-axis “digital motion sensor” for
this application because it is specifically geared toward ultra-low-power
applications.
This chip (IC3) contains a three-axis
MEMS accelerometer and a heap of
signal processing hardware that can
be configured to detect device orientation, free-fall events and tap or
double-tap events on any axis. It can
detect activity and put itself into a lowpower state when it senses inactivity,
waking itself up again autonomously.
I took advantage of the orientation
function to flip the display the right
way up, the single tap function to
change modes and the activity/inactivity function to turn the SmartProbe
on and off.
The device supports a range of
sampling rates and draws anywhere
between 500nA and 90µA when operating. Lower data rates result in lower
operating currents, but some features
we need won’t work at the very lowest data rates. For this reason, we run
the accelerometer at 400 samples per
second when active, dropping to 200
samples per second when ‘off’.
This gives us an ‘off’ power consumption of somewhere around
12-20µA. The data sheet says the consumption will be 12µA in the mode
and data rate we use, but that is specified at 1.8V and 25°C. The data provides no help in understanding what
the consumption will be at higher temperatures or with voltages up to 3.0V,
as it will experience in our circuit.
No data usually means you can
safely assume it will be worse. My
measurements show consumption
closer to 16-20µA with our battery
voltage range and my (unairconditioned) room temperature.
While that is higher than the published figures, I think it is still pretty
amazing performance considering the
chip is taking three 14-bit accelerometer samples every 5ms and pushing
them through a fairly complex digital
signal processing chain.
Hardware-wise, the LIS2DW12 is
very nice; it has just 12 pins, requires
no external components and costs just
$2.50 in single quantities. The downside is that it is only available in a 2
× 2mm leadless package. Fortunately,
it does not have a thermal pad, so it is
easier to hand-solder than some chips
I have come across.
Fig.3: the left and middle diagrams show the voltages on the analog switch in the off state with +50V and -50V applied to
the input, respectively. The rightmost diagram shows them when the switch is on.
36
Silicon Chip
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siliconchip.com.au
It is a complex device from a firmware perspective, but I took the time
to write a (reasonably) comprehensive driver, since I intend to use this
chip again.
Power supply
The power supply scheme is
straightforward, as shown in Fig.4.
There are two power rails: Vbat,
which is derived from a lithium coin
cell and is always available, plus a
3.3V (3V3) rail that is only available
when the SmartProbe is on. The 3.3V
rail is derived from the coin cell via
a boost converter based around IC4, a
TPS61033.
The boost converter is enabled by
the PWR_ON signal from the microcontroller, so the display, analog front
end and beeper are only powered
when the SmartProbe is on. The shutdown leakage current of the TPS61033
is specified at 0.1µA, so well within
our meagre power budget.
The Vbat supply is the diode-OR
combination of the coin cell voltage
and the 3.3V supply. The upshot of
this is that Vbat will be approximately
3.3V while the device is on, but will
fall to very near the battery voltage
when asleep. Both the accelerometer
and microcontroller will happily operate at any voltage between 3.6V and
1.8V, so this is not a problem for them.
I used a pair of schottky diodes to
combine the supplies to minimise
the forward drop, keeping it to only
about 0.2V at the low currents drawn
in standby mode.
Firmware
The firmware architecture is shown
in Fig.5. The software consists of a
main loop, shown at the top, and four
asynchronous tasks triggered by interrupts, shown at the bottom. Some of
these asynchronous tasks communicate with the main loop via a few
shared data registers and flags.
When an interrupt occurs, the processor stops what it is doing and starts
running code from the appropriate
interrupt service routine (ISR).
When the code starts from reset,
the microcontroller core and onboard
peripherals are initialised. This
includes such things as setting up the
microcontroller clocks, the I2C peripheral, PWM, timers and the like. This
only needs to be done once, because
when the microcontroller is stopped,
the RAM contents and register data
are retained.
After this, the external peripherals
are initialised via their drivers. This
involves enabling the boost converter,
initialising the accelerometer and the
OLED display. This step is repeated
each time the SmartProbe awakens
because the display driver’s configuration registers are lost when the 3V3
rail is disabled.
We also reconfigure the accelerometer, even though it is never shut down
completely. We do, however, disable
some of its functions before putting
the microcontroller into sleep mode,
so it is easier just to reprogram it completely when it wakes up.
Once everything is initialised, we
enter the main loop proper. Here, we
check if the accelerometer has detected
a period of inactivity and put itself into
low-power mode. If it has, we proceed
to put the SmartProbe into ‘off’ mode,
as described below.
If it is still active, we check if fresh
data is available from the ADC sampling task. If not, we loop back and
repeat the cycle, checking continuously for inactivity and new data.
When fresh ADC data is available
(approximately twice per second),
the display is updated according to
the operating mode and taking into
account the orientation of the SmartProbe. This routine also takes care
of the auto-ranging and over-voltage
detection.
ADC sampling
The ADC sampling routine operates independently of the main loop,
triggered every 500ms by a repeating
timer. The analog-to-digital converter
(ADC) peripheral within this microcontroller is extremely flexible. It is a
Fig.4: the 3.3V power
rail is derived from the
coin cell voltage via a
boost converter. This
is disabled when the
SmartProbe is ‘off’ but
the microcontroller and
accelerometer remain
powered by the Vbat rail.
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Fig.5: the firmware consists of a
main loop and four asynchronous
tasks, as described in the text. They
communicate with each other via a
few shared data and status registers
(not shown).
12-bit successive approximation converter with an input multiplexer that
can handle up to 18 input channels.
Sixteen of the channels can be connected to input pins (not all of which
are available on the 20-pin version of
the chip), while two can be connected
to internal sources. One of these is a
1.2V bandgap voltage reference. The
ADC also includes a zero-calibration
feature, which we use each time the
SmartProbe becomes active.
The ADC can be configured to
July 2025 37
Table 1 – STM32L031F6P6 power saving modes
Power Mode Core
Peripherals
RAM/Registers
Wake-up
Run
On
On
Retained
Not Applicable
Sleep
Off
On
Retained
Any Peripheral
Stop
Off
Off
Retained
External interrupts, low-power peripherals, RTC, watchdog
Standby
Off
Off
Lost
RTC, watchdog, wake-up pin
automatically scan and convert channels in a sequence. It also has a hardware oversampling capability. If this
is enabled, the ADC will take a series
of samples and average the results for
each channel in the sequence.
I used these features to create a sampling regime that eliminates a lot of
the mains-frequency interference that
would otherwise make achieving stable readings difficult.
If we take many samples of a signal over an integral number of mains
cycles and average them, any mains
frequency component will average to
zero. This is because the average of
any sinusoidal signal over a full cycle
is zero. So, if we make the ADC sample and average each input over one or
more 20ms intervals, any 50Hz component will be eliminated.
In the SmartProbe, the clock division options available to us mean that
we can’t quite do this perfectly. The
best we can manage is to take the 256
samples of each input over a period of
59.05ms – very close to three mains
cycles. This means the mains cancellation will not be perfect, but we should
still reduce it by 34dB (50 times) or
thereabouts, which helps a lot.
This oversampling and averaging
also serves as a simple low-pass filter, helping to smooth out any small
perturbations in the voltage being
measured.
The ADC is therefore set up to convert four inputs in sequence: the high
and low range voltage measurement
inputs, the offset voltage and the internal reference. Each is sampled 256
times, and the results averaged twice
per second. Once configured, all this
happens more-or-less automatically.
An interrupt is triggered at the end
of each conversion sequence, at which
point we need to translate the averaged
ADC readings into absolute voltages
that we can display. The ADC output
is ratiometric with the Vbat power
rail – that means its output code is a
measure of the input voltage as a fraction of Vbat.
Vbat is nominally 3.3V when the
38
Silicon Chip
SmartProbe is on, but this voltage is
not regulated to the extent that would
allow conversion to absolute voltages
at the level of accuracy we want.
Fortunately, there is a way around
this, using the internal bandgap reference. This has a nominal output of
1.2V and pretty good stability. When
the chip is manufactured, the value
of this internal reference is measured
by the ADC while the supply voltage
is fixed at a fairly precise 3.00V, and
the resulting code burned into non-
volatile memory.
The firmware uses this code,
together with the real-time measurement of the internal reference, to calculate the Vbat voltage on each measurement cycle.
Knowing the supply voltage allows
us to determine the absolute value of
the input voltages. It is then only a
matter of subtracting the offset voltage from each of the input voltages to
determine the voltage across the lower
resistor in each divider as a signed
integer in units of millivolts. These
are later adjusted for the divider attenuation in the display update routine.
When new values are calculated,
they are stored in shared memory, and
the flag set to let the main loop know
that new data is available.
Continuity mode & beeper
The accelerometer is set up to detect
single-tap events in the ‘vertical’ axis
of the smart probe (ie, the top or bottom surface when looking at the display) and assert the interrupt line. The
associated interrupt service routine
responds by switching modes: opening or closing the analog switch and
setting the offset voltage appropriately.
A short tone sounds when changing modes – a higher frequency when
switching to voltage mode, and a lower
frequency when switching to continuity mode.
The beeper driver makes use of the
M0+ core’s dedicated tick timer, which
is usually set to provide a system tick
interrupt every millisecond. A tone is
initiated by calling a driver function
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specifying the desired frequency and
duration. The function starts the tone
playing at the appropriate frequency,
then returns. The tone is automatically
terminated after the requisite number
of 1ms ticks elapse.
It is important (to me anyway) that
the continuity beeper has a very fast
response. The ADC samples are only
updated every 500ms, which is fine for
the display, but way too slow for the
beep. Therefore, I used a comparator,
as mentioned earlier.
One of the two onboard comparators is configured to compare the
low-range input voltage with a fixed
internal voltage set to ¼ of the internal 1.2V reference. If the voltage at the
input pin falls below 0.6V, a flag is set
to indicate continuity. If it is above
this level, the flag is cleared. The comparator output flag is sampled every
system tick and the continuity beep
is sounded if it is set.
Low power operation
We mentioned above that the accelerometer is configured to detect a
period of inactivity and autonomously
put itself into a low-power mode.
When the microcontroller detects this
has occurred, the rest of the circuit
must be shut down until the accelerometer indicates activity has resumed.
We have seen that the accelerometer
consumes up to 20µA in its low-power
mode, and we have a total design target consumption of 27µA or less. This
leaves us with just a few microamps for
everything else, including the microcontroller.
The Cortex M0+ architecture supports a variety of low-power modes
with differing levels of power consumption. The trade-off for lower
power is longer wake-up times and
more limited wake-up functionality.
Table 1 shows a (very) simplified
chart of the available modes and
their key differences. Every one of
the modes shown in the table has several variations, and it is entirely possible for a lower power mode to consume more than a higher power mode
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depending on the exact configuration.
“Run” is the normal operating mode
of the microcontroller and has the
maximum power consumption; the
core and all peripherals are operating. The easiest way to reduce power
in this mode (or any mode where the
clocks are operating) is to reduce the
frequency of the system clock below
its maximum of 32MHz. I use a 3MHz
system clock in the SmartProbe for
this reason.
In “Sleep” mode, the core clock is
disabled, but the peripherals remain
fully operational. RAM and register
contents are preserved. This allows
for a very fast wake-up (in the order of
0.35µs) but comes at the cost of around
1mA current consumption at 16MHz.
As the peripherals continue to operate,
pretty much any of them can wake the
processor up.
“Stop” mode, on the other hand,
has the potential to reduce power consumption to the sub-microamp level.
This is the mode I used for the SmartProbe when it’s ‘off’. Here, the core
and most peripheral clocks are halted;
only the real-time clock and watchdog timer continue to run if they are
enabled (which they aren’t). Volatile
memory is retained.
Several possible sources can wake
the microcontroller from stop mode,
including interrupts triggered by the
states of external pins changing, which
is what we use.
The final low-power mode is
“Standby”. In this mode, almost everything is powered off, including the
RAM and almost all the registers. Only
a very limited selection of wake-up
sources is available, and the wake-up
time is the longest.
Putting the processor into stop mode
is in itself not enough to get the current consumption down to the very
low levels we require. There is quite a
lot to do both within the microcontroller and in the external circuit before
executing the instruction that halts
the processor.
Externally, we shut the OLED display off via an I2C command, shut
down the beeper PWM and turn off
the boost converter. Internally, we stop
the ADC conversion process and the
timer that triggers it, disable the bandgap reference and the buffers that feed
its output to the ADC and the comparator. We also limit the functionality
of the accelerometer to just detecting
activity or inactivity.
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A close-up of the probe
we used for our SmartProbe.
We also put most of the I/O pins into
analog input mode so they look like
high-impedance inputs, minimising
any leakage currents that might otherwise occur. The data sheet suggests
that the digital input schmitt trigger
buffers can be a source of leakage –
hence using the analog input mode.
In fact, leakage current is our number one enemy in ultra-low power circuits such as this, and it can come from
some quite obscure sources.
For example, consider the 4.7kW
I2C pullup resistors. These are pulled
up by one of the microcontroller’s
GPIO pins instead of being directly
connected to the power rail (Vbat) as
one might do normally. Fig.6 shows
why we have to do this. The I2C bus
connects to the micro and the accelerometer, which remain powered up
in stop mode, but also to the display,
which does not.
The display driver’s I2C inputs are
internally protected by diodes connected as shown in the figure. In normal operation, these prevent the input
pin rising more than about 0.6V above
the 3.3V supply or falling more than
0.6V below ground.
However, when the boost converter
is off, the display driver’s positive
power rail is at 0V, allowing a leakage current path from Vbat to ground
via the I2C pullups, as shown by the
red paths.
If Vbat was at 2.5V and the protection diode forward drop was 0.5V,
there would be more than 850µA
leakage in total. This is 30 times more
current than our target, so clearly not
acceptable! Powering the pullups
from a GPIO pin that can be put into
a high-impedance state eliminates this
problem.
Once all the internal and external
extraneous current consumers are
dealt with, we are ready to stop the
microcontroller core and peripherals.
We just have to set or clear a few bits
in various control registers to ensure
the core enters the correct low-power
mode and that it wakes up due to the
right stimulus with the right clock
source.
We have to disable all interrupt
sources except the external interrupt
pin associated with the accelerometer, and globally disable interrupts.
Finally, we can execute a “Wait for
Interrupt” (WFI) instruction that stops
the core until an interrupt is received.
It might seem odd that we globally
disable interrupts if we want to wake
up due to an interrupt, but the way it
works is that the peripheral’s interrupt
flag does the waking (in this case the
external interrupt) regardless of the
state of the global interrupt enable
flag. By disabling global interrupts, we
ensure that when the processor wakes
up, it continues executing code where
it left off and not in an ISR.
On resumption, we have to undo
all the work we did before entering
low-power mode, restoring the I/O pin
states, enabling the boost converter
and the internal regulators and buffers
we disabled. We then reinitialise the
drivers to start the ADC, the display
and all the rest of the stuff necessary
to resume operation.
Construction
Fig.6: if the I2C bus was pulled up
to Vbat, significant leakage currents
would flow through the pullup
resistors and display driver chip’s
input protection diodes when the 3V3
rail is off.
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The SmartProbe is built on a small
double-sided printed circuit board
coded P9054-04 that measures 54.5
× 29.5mm. Both sides of the board
are fairly tightly packed with surface-mounting parts, although most
are M2012/0805-sized (2.0 × 1.2mm),
so pretty easy to handle. The overlay diagrams, Figs.7 & 8, show where
everything goes.
Start assembly by mounting the
trickiest part, the accelerometer (IC3).
If you are using solder wire, you will
need to apply some flux paste and a
July 2025 39
thin layer of solder to the pads first.
Try to get roughly the same amount of
solder on each pad – if there is too little
on one or two, you risk an open-circuit
connection. If you elect to use solder
paste, try to get a more-or-less even
smear across the footprint.
You can then reflow the chip using
something like a hot air wand, making sure to get it the right way round.
Despite its small size, I found this
package fairly forgiving when it came
to assembly.
Next, solder in the boost converter
chip (REG4) and then the optional
programming connector, CON3, if you
will use it (it isn’t necessary if you
get a pre-programmed chip from our
Online Shop). They should solder in
fairly easily using a fine tip soldering
iron, some good flux and a bit of solder
wick to clean up any bridges.
Mount the rest of the components
on the top side of the board, except
the coin cell holder and the probe connector (CON1), in the order you prefer. I tend to install the finer-pitch and
smaller parts first, working my way up
to the larger ones.
Flip the board over and install the
six passives on the back side, plus the
audio transducer. Finally, add the coin
cell holder and the probe connector
(CON1) to the top side. It is a good idea
to check your work and clean up the
board with a bit of isopropyl alcohol
or another solvent at this point, before
installing the display.
The display’s flat flex cable is soldered directly to the row of pads on
the back of the board. Make sure the
pin 1 designator on the flex is aligned
with the small dot on the board. This
should correspond with the display
being face-up when folded back on
itself. It should be face-down when
the flat flex is straight, and it should
extend over the side of the board nearest the row of pads.
Align the flat flex so that about 1mm
of the PCB pads are visible, and secure
it in place temporarily with a couple
of bits of adhesive tape.
Double-check everything lines up
and tack the display in place by soldering a couple of the pins. I suggest
using two of the signal pins for this,
rather than the pins connected to the
ground plane, as they require a lot
more heat.
If everything still looks good, go
ahead and solder all the pins, taking
care not to create any short circuits.
You can remove the tape and clean up
with a little solvent if you need to, but
keep it away from the display itself.
If you intend to program the microcontroller in-circuit, do that now. You
will need to make a suitable adaptor
to connect the programmer to the flat
flex connector. See the details in the
accompanying panel.
You will have to insert a coin cell
(or otherwise power the microcontroller) while it is being programmed. If
your microcontroller came preprogrammed, you should skip this step.
You can now perform a quick test
by inserting a coin cell into the holder.
You should hear the start-up beep,
and the display should come to life
in voltage mode with a reading close
to 0.000V. The least significant digit
(millivolts) and the sign may move
around a little, but the rest of the digits should be zero.
If you do nothing, the probe should
Figs.7 & 8: follow
these diagrams
to populate the
PCB. Start with
the accelerometer
(IC3), as it is the
fiddliest part to
mount.
40
Silicon Chip
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siliconchip.com.au
switch itself off after five or six seconds, and it should wake up again you
give it a bit of a jiggle.
This is enough to test the basic functionality. If everything is OK, you can
remove the coin cell and fix the display in place with a small piece of
double-sided foam tape. Fold it over
and align the edges of the display glass
with the outer rectangle on the PCB
silkscreen.
Debugging
If there is a problem, do some troubleshooting before fixing the display
in place. If the unit appears dead, first
measure the 3V3 rail to make sure it
is working when the unit is awake.
If 3.3V is not present, check that the
battery voltage is getting to it and the
boost converter enable pin is high. The
latter is a sign that the micro is at least
trying to start the converter and means
the problem is in the boost converter
itself or there is a short on the 3V3 rail.
If the 3V3 rail is fine and you hear
the start-up beep, but the screen
remains blank, the problem is probably in the I2C bus or with the display.
Check the associated components and
the soldering of the display connector.
It is possible to get shorts under the flat
flex that you can’t necessarily see. Use
a multimeter to look for (unwanted)
shorts between adjacent pins if you
suspect this may be the case.
The firmware does have a fair bit
of error-detection built in. If an error
occurs, the beeper emits a short, low
tone (it is fairly quiet, so listen carefully) and displays a small fault icon
on the screen.
If this says “ACC!”, the code
encountered a problem communicating with the accelerometer. If it says
“DIS!”, the problem is with the display
communication, and if it says “SYS!”
the problem is a processor exception,
so probably related to corrupt code.
Mechanical assembly
Once everything is working as
expected, you can prepare the case.
Mark out and cut the opening for the
display and the sound hole according
to Fig.9. The display aperture can be
cut by drilling a series of holes inside
the marking and finishing up to the
line with files. I used a file to put a
chamfer around the display hole –
the exact dimensions are not critical
as this is purely cosmetic.
Drill the holes in each end of the
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Parts List – SmartProbe
1 Hammond 1551JBK 60 × 35 × 15mm black ABS enclosure
[Altronics H9003]
1 double-sided PCB coded P9054-04, 54.5 × 29.5mm
1 BC-2600 SMD CR2032 cell holder (BAT1)
1 CR2032 3V lithium coin cell (BAT1)
1 Wago 2946-2060-471/998-404 single entry SMD terminal block (CON1)
1 Molex 503480-0800 8-pin flat flex connector, 0.5mm pitch
(CON3; optional, for ICSP)
1 X30654 128×64-pixel 3.3V graphic OLED screen with SH1106 controller
(DISP1) [AliExpress 32890183042]
1 WLPH201610M1R0PP or equivalent 1µH 2A+ inductor,
SMD M2012/0805 size (L1)
1 CMT-0525-75-SMT-TR SMD magnetic transducer buzzer (MB1)
1 6mm-long No.6 self-tapping screw
1 size 4 straw sewing needle
1 alligator clip
1 length of medium-duty hookup wire
1 short length of 2mm diameter heatshrink tubing
1 small piece of double-sided foam-cored tape
Semiconductors
1 TP5534-SR quad chopper-stabilised op amp, SOIC-14 (IC1)
1 32-bit STM32L031F6P6 microcontroller programmed with 0411025A.HEX,
TSSOP-20 (IC2)
1 LIS2DW12 ultra-low-power 3-axis accelerometer, LGA-12 2 × 2mm (IC3)
1 TPS61033DRLR adjustable boost regulator, SOT-583 (REG4)
2 ZXMP6A17E6TA 60V 2.7A logic-level P-channel Mosfets, SOT-23-6 (Q1,
Q2)
2 BSS138K 50V 220mA N-channel logic-level Mosfets, SOT-23 (Q3, Q4)
4 BAV99 ultrafast dual series diodes, SOT-23 (D1-D4)
1 SDM40E20LC 20V 400mA dual common-cathode schottky diode,
SOT-23 (D5)
Capacitors (all SMD M2012/0805 size 50V X7R ceramic unless noted)
1 33μF 16V D-case tantalum
4 10μF 16V
8 100nF
1 10nF
5 1nF
1 100pF C0G/NP0
Resistors (all SMD M2012/0805 size, 1% unless noted)
2 2MW ±0.1%
1 1MW
1 680kW ±0.1%
1 510kW
1 220kW
5 100kW
1 51kW ±0.1%
2 4.7kW
1 3kW
3 1.5kW
1 1kW
1 10W
Optional SWD flat flex adaptor
1 double-sided PCB coded P9045-A, 35 × 25mm
1 Molex 503480-0800 8-pin flat flex connector, 0.5mm pitch (CON1)
1 CNC Tech 3220-10-0300-00 10-pin, 1.27mm-pitch box header (CON2)
1 Molex 0150200079 8-way, 0.5mm pitch 100mm flat flex cable
Australia's electronics magazine
July 2025 41
SWD Programming Adaptor
There was no space on the main PCB
for the standard ST Micro SWD/JTAG
programming header, which is a 2×5pin miniature shrouded box header
(1.27mm pin pitch). Thus, a more
compact 8-way FFC connector was
used. This small PCB adapts that to
the more standard connector so that
a programmer can be connected via
a ribbon cable with an IDC plug.
Its circuit is shown in Fig.a.
Because pins 7 & 8 are not connected
to the main board, only the single-wire
debug (SWD) protocol is supported,
not JTAG. Importantly, note that the
pinout of CON1 is reversed compared
to CON3 in Fig.2. That’s because the
FFC is inserted flat, such that the connections are reversed between those
two connectors.
The adaptor is built on a double-
sided PCB that’s coded P9045-A and
measures 35 × 25mm. The assembly should be straightforward, referring to the overlay diagram, Fig.b. The
TP-X pin is provided
to allow a custom
debugging signal to
be generated from the
microcontroller.
When using it, make sure that
the FFC cable is inserted with the
correct orientation between the two
ends. The easiest way to check this
is to verify continuity between the
grounds of the SWD Adaptor board and target board
before connecting the programmer.
Fig.a: this SWD adaptor connects to
the main circuit (Fig.2) via a flat flex
cable (FFC) and allows a standard
ST Micro programmer to connect via
CON2. The FFC is connected such
that it reverses the connections,
making CON1’s pinout
correspond to CON3
in Fig.2.
A close-up
of the Adaptor’s
flex cable is shown above
and the finished PCB below. We have
used some tape on both ends to
provide extra rigidity.
eye off your needle if it is wider than
about 1mm; otherwise, it may be too
big for the connector.
The connector I used for the probe
has a spring operation. You press down
on the small divot at the top to insert or
remove the conductor. When released,
the connector firmly grips the probe.
That, plus the close fit of the hole in
the case, is enough to hold the probe
solidly in place.
Finally, you need to clip out one of
the two PCB mount bosses inside the
case as it interferes with the display.
The one to remove is diagonally opposite the sound hole.
The PCB is secured to the case with
a #6 × 6mm self-tapping screw – see
Figs.10 & 11. You should solder the
ground lead to the PCB before you
finally mount the board. It solders in
from the top (battery) side, then loops
down and up again through the two
strain relief holes to emerge on the
same side. Thread the wire through
the hole in the case before installing
the board into the case.
I used a ground lead with a connector on the far end, so I had to thread
the near end through the case before
soldering it.
Remember to secure the lid to the
case with the two screws provided.
Coin cells are extremely dangerous
for children, and it is mandatory that
they are only accessible with the use
of a tool. You should also be very careful about where you store them. Keep
them in their special child-resistant
packaging until they are required
and always well and truly away from
inquisitive little hands.
Using the SmartProbe
Fig.b: the SWD adaptor PCB
has just two components,
the connectors, plus three
test points.
case to suit the diameter of the ground
lead and probe you choose (the dimensions shown are what we used). Try to
make the probe hole a close, but not
tight, fit with the probe, including its
insulating sleeve. If it is too loose, the
probe may wobble around.
I made my probe from a sewing needle. These are nice and sharp, so good
for probing surface-mount parts, and
42
Silicon Chip
fairly hard, so they last a while. I used
a size 4 straw-type needle, but any needle with a diameter between 0.5mm
and 1.0mm should do. I covered the
needle in heatshrink tubing, leaving it
about 5mm short of either end.
The eye of my needle was a similar
diameter to the shaft, so I could insert
it through the case and into the connector as-is. You may have to cut the
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There is no need to calibrate the
SmartProbe, but you can check its
operation fairly easily with basic test
equipment. The absolute accuracy is
measured by setting a bench supply to
some voltage near the middle of each
range (I used 2V and 30V) and comparing the SmartProbe reading to that
from a known good meter, preferably
one with five or more digits.
The three units I built were all well
within ±25mV on the 5V scale and
250mV on the 50V scale (0.5% of full
scale in each case).
You can get an idea of its precision
by taking a series of readings (the more
the better) and looking at the variation between them. Successive readings should not differ more than about
siliconchip.com.au
±5mV and ±50mV on the two ranges,
respectively. Keep the multimeter connected when you do this, to make sure
the measured voltage does not change.
I measured the current consumption
of the three units I built. The maximum current when on was between
15mA and 25mA, depending on the
cell voltage. This means the average
battery life when on will be around
12 hours. When off, the current consumption was always less than 25µA,
corresponding to a shelf life of about
387 days.
Of course, neither of these is a realistic scenario. However, if we assumed
an on-time of 30 minutes per week
(remember it switches off after five or
six seconds of inaction, so this is 30
minutes of actual measurement time),
a fresh cell should last a little over 4
months.
The SmartProbe won’t replace my
multimeters, but if it becomes the first
piece of test equipment that I reach for,
SC
I will consider that a success!
Fig.9: drill the holes in the ends of the
case to sizes that suit your probe and
ground wire. You want a close (but not tight)
fit, so the probe is held firmly in place.
The programming adaptor connected to the
prototype SmartProbe.
Figs.10 & 11: the
PCB is secured in
the case with a #6 × 6mm
self-tapping screw. The probe
is inserted through the hole
in the case and into its
connector after the PCB is
mounted. Ensure the lid of the
case is secured with the supplied
screws to comply with the safety
requirements for coin cells.
siliconchip.com.au
Australia's electronics magazine
July 2025 43
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By Andrew Levido
Precision
Electronics
Part 9: System Design
In this last article in the Precision Electronics series, we look at the design of a
precision electronics system from the big-picture perspective. We have already covered
a lot of the building blocks; this will bring them together and show how to approach the
design of a whole system.
T
o do this, we will look at a practical
example of moving from a high-level
specification to developing design
goals for each circuit block, then dive
in detail into a couple of the blocks for
good measure.
Before we get into it, I want to summarise some of the key tips and tricks
we have learned from previous articles that might help guide our design.
These are not hard-and-fast rules; they
are just things I have found it helpful
to keep in mind:
• Precision and accuracy are different things. Precision is all about errors
and repeatability, while accuracy is
all about calibration and traceability.
• Break circuits down into bitesized chunks to perform error analysis. Things can get overwhelming if the
circuit being analysed is too complex.
• When like quantities with errors
add or subtract, add the absolute
errors. When quantities with errors
multiply or divide (like an input offset
through a gain), add the relative (proportional) errors.
• Completely uncorrelated random
errors (like white noise) can be added
as the root sum of squares – either
absolute or relative, depending on the
application. This also applies to calculating a DAC’s or ADC’s total unadjusted error (TUE) figure.
• You can easily calibrate or trim
out fixed errors like offset and gain
errors. It is harder to do so for non-
linearities or errors that change with
temperature. The highest-precision
devices use this technique extensively,
often performing calibration before
every reading.
• In general, keep the span of precision signals away from the power rails
or the ends of ADC and DAC ranges
where they coincide with the supply
rails. This is one place where non-
linear errors love to hide.
• Read data sheets carefully, including the graphs. Manufacturers don’t
usually highlight the shortcomings of
their parts in the headline specs. Use
worst-case errors (not typical values)
unless you have a good reason not to.
• Use larger signals and lower gains
where you have a choice. Input-side
errors are magnified by gain stages. The
signal-to-noise ratio can be improved
by using larger signals.
• Reduce noise by limiting circuit
bandwidth and using lower-value
resistors where possible. Oversampling and averaging is a useful form
of bandwidth limitation.
• Reduce cost by using components
with no higher precision than you
absolutely need. Use an error budget
spreadsheet to understand the major
contributors to error and focus on
these first.
The process of top-down design is
kind of the opposite of what we have
done so far, where we looked at individual circuits and calculated their
errors. This time, we will divide the
Fig.1 (left): the highlevel block diagram of
our hypothetical power
supply. This is all we
need to start the design
process.
Fig.2 (below): the error
amplifier in the control
block will most likely
include an inverting,
summing amplifier like
this. If so, the setpoint &
feedback voltages must
be of opposite polarity.
46
Silicon Chip
Australia's electronics magazine
siliconchip.com.au
overall system error up to develop
an error ‘budget’ that will guide the
design of each subsystem.
This sounds very straightforward,
but in practice there is almost always
a certain amount of iteration (even to
the point sometimes of revising the
top-level specifications).
A simple power supply
The example I want to work with is
a simple power supply that can source
a voltage in the range of 0-20V with a
maximum current of 1A. We are not
going to fully design this power supply
here – we are just aiming to develop
the error budget and look at the system considerations including coming
up with a calibration strategy.
I will go through a more detailed
component selection and analysis for
a small part of the circuit, just to show
how I go about it.
Let’s start with some target specifications. We want to be able to set the
voltage in 100mV steps and the current
limit in 10mA steps. This corresponds
to a modest precision of ±0.5% for the
voltage and ±1% for the current setpoint. However, we want to be able to
measure the voltage and current to a
precision of ±0.1% (±20mV and ±1mA
respectively).
These specs are all defined at nominal temperature (25°C). For simplicity’s sake, we will assume that they
should be no worse than 150% of nominal over the operating temperature
range. This is a laboratory instrument,
so I am going to arbitrarily decide that
a range of 5°C to 45°C (25°C ±20°C)
will be adequate.
Two-point calibration
The figure below shows a system like the voltage setpoint and regulation circuit in our example power supply. The ideal transfer function for the system
is y = kw, where k is the design gain (for example, some number of millivolts
per LSB), w is the input digital code and y is the output quantity. There is gain,
but no offset, in this ideal system.
A real system may have both a gain error and an offset error, as shown on
the bottom of the figure. Here, the gain (m) is close but not equal to the ideal
gain, k, and there is a non-zero offset, b. The firmware correction block shown
on the left takes in the input code w and applies correction gain n and offset
c to produce a corrected code x, such that the output of the hardware system
y has the ideal relationship with the input code w.
If we measure the hardware system’s transfer function (ie, find the gain [m]
and offset [b]), we can calculate the compensating gain n and offset c. Twopoint calibration is the simplest process that allows us to calculate these correction factors.
The calibration cycle starts by setting the correction gain n to unity and the
correction offset c to zero. This means DAC code x will equal the raw code w.
The calibration firmware then sets the code to a value near the bottom end of
the span (wL), as shown in the figure, and we measure the output quantity (yL)
using an external meter. This value is provided to the firmware.
Next, the calibration routine sets code w to one near the top of the span
(wH). This is also measured and entered into the instrument.
Now the firmware can calculate the hardware’s transfer function coefficients
using the equations m = (yH – yL) ÷ (xH – xL) and b = yL – mxL. With this done,
the correction factors can be calculated from the relations n = k ÷ m and c = –b
÷ m. These factors would be stored in non-volatile memory and used to correct
the DAC code to compensate for the gain and offset errors in the hardware.
Two-point calibration has the advantage of being very simple to implement.
You can improve on it by using more points (called multi-point calibration), and
deriving the hardware transfer function from a suitable line-of-best-fit algorithm.
High-level circuit design
Designs should start with a simplified block diagram, as shown in Fig.1.
Here, a microcontroller (not shown)
feeds a pair of DACs which, together
with the signal conditioning blocks,
create the voltage and current setpoints that are applied to the power
supply control circuit. This circuit regulates the output voltage and manages
the current limiting.
Feedback of the output voltage and
current is necessary to allow the control circuit to regulate properly.
The voltage feedback for the control
circuit comes from the power supply
output via high-impedance buffer 1.
This unity-gain buffer is required to
minimise the current drawn from the
output terminal, as this will affect the
siliconchip.com.au
current measurement. The same buffer provides the voltage measurement
input to ADC2 via a voltage divider
and a second unity-gain buffer.
Current sensing is provided via a
high-side shunt resistor and instrumentation amplifier. This feeds both
the control circuit and the current
measurement function via ADC1. We
will need two DACs since we have
to provide both setpoints simultaneously, but we can get away with one
ADC with an input multiplexer, since
we can sample the current and voltage alternately.
Error amplifier
The control circuit is most likely
going to contain error amplifiers made
Australia's electronics magazine
using an inverting, summing amplifier
like that shown in Fig.2. This topology
has two implications for our design.
First, it means that the senses of the
setpoint and feedback signals need to
be opposite, so the error amplifier sees
the difference between the output and
the setpoint.
If the setpoint is negative, as shown,
a setpoint increase (ie, a more negative
voltage) will cause the error amplifier
output to increase in a positive direction, driving the output voltage or
current limit higher. Similarly, if the
feedback level increases, the error amp
output will be forced lower, reducing
the output voltage or current limit.
Secondly, the error amplifier summing junction (the op amp’s inverting
July 2025 47
input) sits at 0V and actually sums currents determined by the input voltages
and the values of the two input resistors, R1 and R2.
The result is that the full-scale setpoint voltage and full-scale feedback
voltages do not have to be the same,
since we can adjust the values of the
resistors to make their full-scale currents equal.
We do have to be concerned with
the precision of the ratio between the
resistor values, as any deviation will
cause an error in the setpoint. Fortunately, we do not have to worry about
anything further into the controller
circuity, as any offset and gain errors
here are eliminated by the action of
the feedback.
The same is true for non-linearities
in this part of the circuit, although if
they are extreme, they can impact control loop stability.
Block diagrams & error budget
Fig.3 shows the circuit in Fig.1 broken down into four ‘signal chains’, one
each for the voltage and current controls, and one each for voltage and current sensing. This is a great way to get
a handle on just which circuit block
impacts the overall device precision.
Some of the blocks appear in multiple chains; for example, the output
voltage buffer appears in all the chains.
In other cases, like the setpoint signal
conditioning block, there are separate
but identical blocks.
The task, then, is to take the overall
precision specification for each signal
chain and allocate it to the various circuit blocks. The duplication and repetition of blocks described above makes
this a slightly complex process.
I used an error budget spreadsheet
like that of Table 1. I have listed
the unique circuit blocks down the
left-hand side and the four signal
chains across the top.
Where a particular circuit block
appears in a signal chain, I entered
the appropriate number in the matrix.
I then made a stab at setting an error
budget for each circuit block down the
left side, while checking the totals in
blue along the bottom compared to the
targets shown in purple.
It is best to start from the most difficult chain (the current sensing chain
in this case) and work from there. You
can see that some of the error budgets
end up better than the target, which is
OK at this stage.
There is no point in allocating the
error budget down to the nth degree
in this process. You can see that the
budget here shows the current-sensing
signal chain to be just over the target.
This is near enough for this stage in
the design cycle.
It does take a bit of experience to
work out what are reasonable error
assumptions for each particular block,
but hopefully, some of the previous
articles in this series have given you a
feel for it. Clearly, a unity-gain buffer
using a zero-drift op amp will have a
much lower error than a 16-bit ADC.
The next step is to work through
the design, block by block, selecting
components and topologies that will
meet the targets for each subcircuit. I
recommend starting with the subsection where you think it will be most
difficult to achieve the target precision.
This may not be the area with the highest precision requirement.
Calibration strategy
Fig.3: the power supply functions can be broken down into these four signal
chains. Some of the circuit blocks appear in multiple chains, complicating
the process of assigning error budgets to each one.
The errors in Table 1 are trimmed
errors, so we need to have some idea
of our calibration strategy to translate these to untrimmed errors for the
design process.
To keep things simple, for this
power supply, I plan to perform calibration manually when we build
the supply and every now and again
thereafter. This eliminates the need for
in-system calibration circuitry. However, this implies that our calibration
will only be able to improve fixed gain
and offset errors at the nominal temperature.
The minimum required to do this
is two-point calibration (described in
detail in the accompanying panel).
This means calculating and storing an
offset and a gain calibration value for
each of the four signal chains.
Australia's electronics magazine
siliconchip.com.au
48
Silicon Chip
In practice, the calibration of the setpoint and measurement chains can be
done simultaneously. For example, to
calibrate the two voltage signal chains,
we would set the voltage at some low
value (say 1.0V) and measure the
actual terminal voltage with an external meter with sufficient resolution.
We would do the same at some high
value (say, 19.0V).
Once entered into the system, these
two values can be used to calculate
calibration coefficients for the setpoint
chain by comparing them with the
nominal setpoint, and the measurement chain by comparing them with
the values read by the ADC.
Given this calibration strategy, I
have made the assumption that we can
calibrate fixed offset and gain errors
down to 5% of their untrimmed values (ie, we can calibrate out 95% of the
error). Non-linear errors and temperature dependent errors are not reduced
at all by this method.
Voltage setpoint design
I will go through the process in some
detail for a small part of the circuit to
show you the idea, starting with the
voltage setpoint circuit, although I
have included the full set of error calculations in Table 2.
To do this, we need to define some
full-scale voltage levels. We will start
by assuming that we have a 3.3V logic
supply for the microcontroller and
±5V analog supplies, as well as the
24V unregulated supply used for the
output.
We would like to use a low-cost
serial DAC, since the setpoint precision requirements are not strenuous.
This will have to run from 3.3V to
interface with the micro, so we will
Table 1 – error targets for each circuit block (in purple) and the resulting error (in blue)
Circuit Block
Error <at>
25°C
Additional Voltage Current
Error ±20°C Setpoint Setpoint
Voltage
Sensing
Current
Sensing
DAC
0.250%
0.125%
1
1
Setpoint signal
conditioning
0.100%
0.050%
1
1
Summing node
0.013%
0.006%
1
1
Buffer
0.013%
0.006%
1
1
2
1
Current sensing
0.040%
0.020%
Voltage divider
0.013%
0.006%
1
ADC
0.050%
0.025%
1
Voltage reference
0.003%
0.001%
1
1
1
1
1
1
1
Target error <at> 25°C
0.500%
1.000%
0.100%
0.100%
Target additional error ± 20°C
0.250%
0.500%
0.050%
0.050%
Total <at> 25°C
0.378%
0.418%
0.090%
0.105%
Total additional ± 20°C
0.189%
0.209%
0.045%
0.053%
Total error 5°C to 45°C
0.566%
0.626%
0.135%
0.158%
be limited to a full-scale analog range
somewhere below this level. If we
select a full-scale voltage of 2.5V, we
will have a wide choice of low-cost
external voltage references.
One of our precision design rules of
thumb is that we should not trust analog values as they approach the power
supply limits. We will have a DAC output that varies between 0V and 2.5V,
depending on the input code.
Given a resistor-string DAC with
a 3.3V supply, we can be reasonably
comfortable at the top of the range,
since there is plenty of headroom
between the highest tap voltage (very
close to 2.5V) and the analog supply
rail (3.3V).
However, the bottom end of the
DAC’s resistor string will be grounded,
as will the DAC’s analog circuitry, so
we cannot count on the lower end of
the range. This is a problem because
it suggests that we will lose accuracy
near the bottom of the range and/or
might not be able to set the output voltage or current limit right down to zero.
You will recall that we need a negative setpoint signal, so we anticipated a
signal conditioning block between the
DAC and the controller. The simplest
way to do this would be to use a unity-
gain inverting amplifier, as shown at
the top of Fig.4. With a 2.5V reference,
this gives us an output in the range 0V
to -2.5V, as shown in the graph on the
right of the figure.
Unfortunately, this does nothing to
help with our near-zero problem.
However, if we use a difference
amplifier as shown at the bottom of
Fig.4, we shift the DAC output down
by Vref, rather than inverting it. The
upshot is that we will get very nearly a
true 0V output when the DAC is at full
scale. As the DAC output approaches
At Nominal 25°C
Error
Additional error over 25 ±20°C
Abs. Error
Rel. Error
Abs. Error
Rel. Error
2 DAC Offset Error: ±15mV, 10µV/°C
15mV
0.750%
200µV
0.010%
3 DAC Gain Error: ±1%, 3ppm/°C
20mV
1.000%
60µV
0.003%
4 DAC INL: ±4LSB
2mV
0.098%
0mV
0.000%
5 Trimmed Error: 5% of (Line 2 + Line 3, root sum squares) + Line 4
3.2mV
0.160%
208.8µV
0.010%
1 DAC: MCP48FVB22, 12-bit, Two Channels, SPI
6 Temperature Drift Error: Line 2 + Line 3, root sum of squares
Setpoint Signal Conditioning: TPA1834 Op Amp, Quad Zero Drift
1 Op Amp Offset Error: ±7µV, ±0.04µV/°C
7µV
0.000%
800nV
0.000%
2 Op Amp Gain Resistor R1/R2: Vishay ACASA, 0.1%, 0.05% matched, 15ppm/°C
1mV
0.050%
600µV
0.030%
3 Trimmed error 5% of (Line 1 + Line 2)
50.4µV
0.003%
600.8µV
0.030%
4 Temperature Drift Error: Line 1 × Line 2
Table 2 – detailed error calculations each signal block (see overleaf for the rest of the table; LSB = least significant bit).
Absolute error values are with respect to 2V out
July 2025 49
Table 2 continued...
At Nominal 25°C
Error
Abs. Error
Rel. Error
Additional error over 25 ±20°C)
Abs. Error
Rel. Error
Summing Node: RN73C2A, 0.1%, 10ppm/°C
1 Summing Node Gain Error
0.200%
2 Trimmed error 5% of Line 1
0.010%
0.020%
3 Temperature Drift Error (Line 1)
0.020%
Buffer: TPA1834 Op Amp, Quad Zero Drift
1 Op Amp Offset Error: ±7µV, ±0.04µV/°C
7µV
2 Trimmed error 5% of Line 1
0.000%
800nV
0.000%
0.000%
3 Temperature Drift Error (Line 1)
0.000%
ADC: ADS1115, ∆∑, 16-bit, 4CH, I2C
1 ADC Offset Error: ±3LSB, 0.005LSB/°C
114.4µV
0.005%
3.1µV
0.000%
2 ADC Gain Error: ±0.15%, 40ppm°C
3.8mv
0.150%
2mV
0.080%
3 ADC INL: ±1LSB
38.1µV
0.002%
4 Trimmed error 5% of (Line 1 + Line 2, root sum squares) + Line 3
225.7µV
0.056%
2mV
0.080%
5 Temperature Drift Error (Line 1 + Line 2, root sum of squares)
Current Sense
1 Shunt Error 1Ω: VMP-1R00-1.0-U, 1%, 20ppm/°C
10mΩ
1.000%
400µΩ
0.040%
2 In Amp: INA821: VOS ±35µv, 0.4V/°C
35µV
0.002%
8µV
0.002%
3 In Amp Input Voltage Error Total: Line 1 + Line 2
10mV
1.004%
408µV
0.041%
4 In Amp Gain Resistor RG: ERA-6ARB333V (0.1%, 10ppm/°C)
0.100%
0.020%
5 In Amp gain error (0.015% ±35ppm/°C)
0.015%
0.070%
6 Total In Amp gain error (Line 4 × Line 5)
0.115%
0.090%
7 Trimmed error 3% of (Line 3 × Line 6)
677.9µV
0.034%
8 Untrimmable temperature drift error (Line 2 × Line 3)
2.6mV
0.131%
Voltage Sense Divider: RN73C2A, 0.1%, 10ppm/°C
1 Divider gain error
0.200%
2 Trimmed error 5% of Line 1
0.010%
0.020%
3 Temperature drift error (Line 1)
0.020%
Reference: REF3425TD, 2.5V, 0.05%, 6ppm/°C
1 VREF error
0.050%
2 Trimmed error 5% of Line 1
0.003%
0.012%
3 Temperature drift error (Line 1)
0.012%
ADC Iteration #2: AD7705, ∆∑, 16-bit, 4CH, SPI
1 ADC Offset Error: 0.0 (with internal cal), 0.5µV/°C
0V
0.000%
10µV
0.000%
2 ADC Gain Error: 0.0 (with internal cal), 0.5ppm/°C
0µV
0.000%
25µV
0.001%
3 ADC INL: ±0.003% FSR
75µV
0.003%
4 Trimmed error 5% of (Line 1 + Line 2, root sum squares) + Line 3
75µV
0.019%
26.9µV
0.001%
5 Temperature drift error (Line 1 + Line 2, root sum of squares)
Current Sense Iteration #2
1 Shunt Error 1Ω: VMP-1R00-1.0-U, 1%, 20ppm/°C
10mΩ
1.000%
400µΩ
0.040%
2 In Amp: AD8223: VOS ±100µv, 1.0µV/°C
100µV
0.005%
20µV
0.004%
3 In Amp Input Voltage Error Total : Line 1 + Line 2
10.1mV
1.010%
420µV
0.042%
4 In Amp Gain Resistor RG: ERA-6ARB333V(0.1%, 10ppm/°C)
0.100%
0.020%
5 In Amp gain Error (0.02% ±2ppm/°C)
0.020%
0.004%
6 Total In Amp gain error (Line 4 × Line 5)
0.120%
0.024%
7 Trimmed error 3% of (Line 3 × Line 6)
684.8µV
8 Untrimmable temperature drift error (Line 2 × Line 3)
50
Silicon Chip
Australia's electronics magazine
0.034%
1.3mV
0.066%
siliconchip.com.au
zero, the circuit output approaches
-Vref, corresponding to the maximum
output voltage.
By setting the full-scale setpoint
voltage to something less than -Vref;
say, letting -2.0V correspond to a 20V
output, we avoid the very bottom part
of the DAC’s output voltage range and
the errors that may lie there.
The downside is that the full-scale
DAC code now represents a setpoint of
zero and a code near (but above) zero
represents full-scale. This inconvenience is easy to remove in the firmware with a simple subtraction.
So, for the sake of the exercise, we
will set the voltage setpoint range to
0V to -2.0V representing, 0V to 20V,
and the current limit setpoint voltage
to 0 to -2.0V, representing 0A to 1.0A.
We can now select a candidate DAC.
I chose the MCP48FVB22 low-cost
two-channel 12-bit serial DAC from
Microchip for this exercise. Its specifications are shown in the appropriate
section of the error budget table. Since
2V is our full-scale output, I have used
that as the basis for converting between
absolute and relative errors.
The upshot is a DAC error of ±0.16%
at 25°C with another ±0.01% over the
operating temperature range, well
inside our ±0.25% budget.
The errors for the setpoint signal
conditioning are calculated as we have
shown in previous articles. I used a
matched resistor array and a low-cost
zero-drift op amp, which gives us an
overall 25°C error of ±0.003%. In this
case, the resistors’ ±15ppm temperature drift means we have an order of
magnitude more error over the temperature range; however, this is still
well inside the error budget.
The summing node errors are dictated by the matching of the resistors
– in this case, I used ±0.1% tolerance
resistors with ±10ppm/°C drift. The
resulting 25°C and temperature drift
errors are ±0.01% and ±0.02%, respectively. The buffer uses the same zerodrift op amp as the signal conditioning, and this circuit yields errors that
are so low as to be insignificant in our
application.
The results for each of these blocks
(plus the rest, which I will not discuss
in detail) are summarised in Table 3.
This is similar in format to the error
budget table. The calculated errors for
each block are on the left, with the
signal chain errors calculated as we
did earlier.
siliconchip.com.au
Fig.4: using a difference amplifier as shown allows us to avoid using the
very lowest part of the DAC’s output range (errors lie there).
Circuit Block
Error <at>
25°C
Additional Voltage Current
Error ±20°C Setpoint Setpoint
Voltage
Sensing
Current
Sensing
2
1
DAC
0.160%
0.010%
1
1
Setpoint signal
conditioning
0.003%
0.030%
1
1
Summing node
0.010%
0.020%
1
1
Buffer
0.000%
0.000%
1
1
Current sensing
0.034%
0.131%
Voltage divider
0.010%
0.020%
1
ADC
0.056%
0.080%
1
1
Voltage reference
0.003%
0.012%
1
1
1
1
1
1
Target error <at> 25°C
0.500%
1.000%
0.100%
0.100%
Target additional error ± 20°C
0.250%
0.500%
0.050%
0.050%
Total <at> 25°C
0.175%
0.209%
0.069%
0.093%
Total additional ± 20°C
0.072%
0.203%
0.112%
0.223%
Total error 5°C to 45°C
0.248%
0.412%
0.181%
0.316%
Table 3 – we have met the targets for most errors but the voltage and current sensing circuits
All the resulting 25°C signal chain
errors are lower than or equal to the
targets we set, but the temperature drift
errors, and therefore the total errors,
for the voltage and current sensing
functions (shown in red) are not.
Second iteration
It is not at all unusual to find some
problems such as this on the first pass.
The process we have gone through –
specifically, the detailed error calculation spreadsheet – makes it easy to
spot the problem areas. These are the
ADC’s ±0.08% temperature-dependent
error, which contributes to both signal
chains, and the current-sensing circuit’s temperature-dependent errors.
The error calculation table shows us
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that ADC error is entirely due to the
temperature dependency of the ADC’s
gain, so the only real solution is to find
a better one. The device I originally
chose, the ADS1115, costs around $7
and has a gain drift of ±40ppm/°C,
which I thought was appropriate for
this design.
The table shows us that we need to
get the gain drift down to ±10ppm/°C,
or ideally lower, if we are to make a
meaningful improvement.
The slightly fancier AD7705 is a
good candidate. It features automatic
calibration that all but eliminates fixed
offset and gain errors, and an impressively low gain drift of ±0.5ppm/°C.
This ADC costs about twice as much
as the ADS1115, so we have to decide
July 2025 51
Table 4 – by addressing critical areas, we have achieved our targets for all signal chains
Circuit Block
Error <at>
25°C
Additional Voltage Current
Error ±20°C Setpoint Setpoint
Voltage
Sensing
Current
Sensing
DAC
0.160%
0.010%
1
1
Setpoint signal
conditioning
0.003%
0.030%
1
1
Summing node
0.010%
0.020%
1
1
Buffer
0.000%
0.000%
1
1
2
1
Current sensing
0.034%
0.066%
Voltage divider
0.010%
0.020%
1
ADC
0.019%
0.001%
1
Voltage reference
0.003%
0.012%
1
1
1
1
1
1
1
Target error <at> 25°C
0.500%
1.000%
0.100%
0.100%
Target additional error ± 20°C
0.250%
0.500%
0.050%
0.050%
Total <at> 25°C
0.175%
0.209%
0.031%
0.055%
Total additional ± 20°C
0.072%
0.138%
0.033%
0.079%
Total error 5°C to 45°C
0.248%
0.348%
0.064%
0.135%
whether the improvement gained from
the substitution is worthwhile or not.
This is the type of judgement call
you will frequently have to make, but
with a detailed analysis such as this,
we have the tools to decide where to
spend money to get the best results. I
decided to go for it – an easy decision,
because this is just an exercise!
The next area of temperature drift
error is the current sensing circuit.
The error tables show that most of
the error comes from the instrumentation amplifier’s gain drift. Initially, I
used an INA821 because we used it in
an earlier article. However, we could
replace it with the similarly priced
AD8223.
This has a significantly worse offset
voltage (100µV vs 35µV), but much
better gain drift (±2ppm/°C compared
to ±35ppm/°C). Replacing the op amp
reduces the current sense circuit’s temperature error from 0.22% to 0.08%.
This illustrates another type of
trade-off we sometimes encounter –
trading off one specification against
another in similarly priced chips.
Building an error budget like I have
done here is extremely helpful in
working out which parameters really
matter for your application.
So, with the changes we have
made in iteration 2 (Table 4), we have
exceeded our target 25°C specifications by a factor of about two across
the board. We have also met the total
error over the temperature range across
the board, even though the drift figure
for the current sense circuit is still a
bit higher than the target.
This is another useful lesson – while
we have to set targets for both fixed
and variable errors, we can trade off
underperformance in one with overperformance in the other.
Conclusions
With this, we have reached the end
of the Precision Electronics series. If I
have one closing message for the prospective precision circuit designer,
it would be that a bit of time spent
at the beginning with a pile of data
sheets and a spreadsheet will be paid
back many times over when it comes
to building and validation of your
designs.
I am as keen as anyone to lay out a
board, get my hands on a prototype
and sit down at the bench, but I have
learned from experience that if I skip
the homework, I will pay for it later in
frustration and avoidable rework! SC
Songbird
An easy-to-build project
that is perfect as a gift.
SC6633 ($30 plus postage): Songbird Kit
Choose from one of four colours for the PCB (purple, green, yellow or red). The kit includes nearly all
parts, plus the piezo buzzer, 3D-printed piezo mount and switched battery box (base/stand not
included). See the May 2023 issue for details: siliconchip.au/Article/15785
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Feature by Julian Edgar
There are so many useful
parts just waiting to
be collected in the
consumer goods
that people throw
away. Here’s what
to look for.
SALVAGING PARTS
T
he electronic equipment I build
seems to use a lot of cooling fans
and heatsinks. Those heatsinks range
from the small ones that cool individual transistors up to those that are
200mm or more in length, while the
fans go from tiny ones to 150mm in
diameter. The good news is that, over
the years, I have paid nothing for any
of them!
It isn’t just fans and heatsinks. I also
get free plugs, sockets, switches, bearings, stepper motors, mains filters and
IEC sockets... the list goes on and on.
The trick is to salvage parts from the
electrical consumer goods that others
throw away.
Let’s look now at some of the most
productive discarded goods to salvage.
There are warnings for some items, so
make sure you read them before doing
any disassembly.
Photocopiers
Photocopiers are always worth
salvaging, and the bigger they are,
54
Silicon Chip
the better. I once saw a huge Kodak
commercial printer advertised free
of charge. I just had to take it away. I
knew it was going to be big, but when
I broke a sling trying to hoist it onto a
trailer with my engine crane, I thought
I was defeated.
The company was so eager to get
rid of it that they agreed that I could
dismantle it in their car park. I could
take what I wanted and put the rest
in their skip (it was too big to fit in
the skip without being pulled apart).
I still marvel at the quality of components that I got out of that machine.
But let’s get back to more normal size
photocopiers...
The quality and number of useful
components that you’ll find in a photocopier depends a lot on the specific
machine. Unfortunately, there’s no
way of knowing until you pull it apart.
Some photocopiers have as many five
DC brushless fans, while others have
only two.
Some photocopiers have large
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stepper motors but other use synchronous AC motors, which are much less
useful. Then again, finding out what
you’re getting is part of the excitement of salvaging parts from discarded
equipment.
You’ll find lights and fans inside
all photocopiers. The lights are high-
voltage, high-power incandescent filament bulbs that are used both to illuminate the material to be copied and
also as a heater to cook the toner as the
photocopied sheets are on their way
out of the machine. The latter light
often includes an over-temperature
switch mounted nearby.
In addition, you’ll sometimes find
rows of mains-powered neons or
low-voltage LEDs. The fans consist primarily of conventional PC-type fans;
they often run from 24V but they’ll
work down to 12V without problems.
Sometimes, if you get lucky, you’ll
find a bunch of high-flow squirrel-cage
fans. These are most often mains-
powered, but a few work on 24V DC.
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A typical older photocopier, partway
through disassembly. Photocopiers
are always worth savaging for their
parts; the larger the machine, the
better. You’ll find lenses, front-faced
mirrors, low current and heavyduty switches and often good quality
stepper motors.
Three stepper motors (bottom) and an AC motor with a built-in reduction
gearbox (top) salvaged from a photocopier. The AC motor had an output
shaft speed of just 53 RPM, making it ideal for spinning an advertising sign
or the like.
Two cooling fans, LED lights and incandescent lights.
The latter can also be used as high-power resistors.
All photocopiers contain
at least one very sharp
lens. They are ideal
for use as close-up
magnifying glasses.
There is a lot
of salvageable
hardware
inside a typical
photocopier,
like springs,
pulleys,
machine screws
and self-tapping
screws.
You can also be guaranteed to find
an excellent quality lens (typical focal
length: 180mm) and several mirrors.
The lenses are razor sharp and make
ideal hand magnifying glasses. They’re
large and bright, and some are coated
for better light transmission.
The mirrors are front-faced and of a
length that corresponds to the width of
the photocopy area. Typically, they’re
10 to 20mm wide, so they’re long and
narrow. I haven’t found a lot of use for
them (except, oddly enough, winding high-powered resistors on them),
but if you’re into lasers or other optical systems and need a very low-cost,
high-quality mirror, there are plenty
waiting for you!
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Even if the photocopier’s main
transport system is powered by an
AC motor, there will still be a few
low-voltage stepper motors inside. For
example, if the copier uses a document
feeder, there’ll be a stepper motor buried in that part of the machine.
However, occasionally you stumble
across gold – huge stepper motors with
built-in reduction gearboxes. These are
highly prized (and if you don’t want
them, you can make a good profit selling them). They can be used to drive
robots or three-axis milling machines,
or be driven backwards and used as
surprisingly powerful alternators.
There are two completely different
classes of switches that you’ll find
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in a copier. The most numerous are
the tiny tactile PCB-mounted press-
buttons mounted behind the membrane keypad.
If these are extracted from the PCB
by using a heat gun directed at the solder side, while at the same time a pair
of pointy-nosed pliers is used to pull
them out, many can be salvaged in a
very short time.
There will also be another pair of
high-current switches: the main on/
off switch (normally on the back of
the photocopier) and a pushbutton
switch that goes open-circuit when
the top half of the copier is pivoted
up for repair or toner replacement.
The latter two switches are definitely
July 2025 55
Micromite-Explore 40
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mind. If it was recently powered or
you aren’t sure, use our Capacitor Discharger (December 2024; siliconchip.
au/Article/17310) to make sure they
are fully discharged as soon as you
can access them.
This list of parts hasn’t been exhaustive – I haven’t mentioned the LED displays, the electromechanical counter,
the electric clutches, bearings or
shafts. There are usually plenty of good
bits to salvage.
Even if you don’t keep a lot of stuff,
pulling apart a photocopier is a fun
exercise in itself – it’s fascinating to see
how the engineers have fitted a complex machine into a compact package.
used it as a cooling spray on a turbo
car intercooler!
Washing machines
siliconchip.au/Article/16677
Coffee machines
Includes the PCB and all onboard parts.
Audio Breakout board and Pico BackPack are
sold separately.
You wouldn’t normally think of
looking inside a discarded espresso
coffee machine for good parts – but, in
fact, there’s a bunch of useful goodies
inside. In addition to switches, pilot
lights (sometimes neon, sometimes
LED), stainless steel fasteners and normally closed temperature switches,
there’s the pump – and what a pump!
Coffee machines contain a mains-
powered oscillating (sometimes
rotary) water pump that is capable
of very high pressures – over 15bar
(218psi). These pumps are fantastic
where you want highly atomised water
– just use high-pressure hose and fittings to attach the pump to a good
quality brass misting nozzle.
You cannot run the pump continuously (it gets too hot), but if you cycle
it on and off, it will be fine. When
salvaging the pump, don’t forget to
also get the rubber mounts on which
it sits – in operation, these pumps
vibrate at 50Hz. I’ve actually run one
of these pumps from an inverter and
Washing machines have changed
a lot over the years. Whereas once
a typical washing machine was a
top-loading, belt-driven design with
mechanical timer controls, machines
now include technology like directdrive motors, fully electronic controls
and plenty of wiring. Those aspects
make any washing machine built in
the last 20 years worthy of salvaging
for its internal parts.
All washing machines have a powerful electric motor inside. Most
machines are belt-driven; that is,
they use an electric motor that’s easily removed and can then be used as
a standalone motor to drive anything
you want – from a workshop sander
to a fan.
If removing the motor, don’t forget
to also get the start and run capacitor, if fitted.
Some washing machines – notably
Fisher & Paykel designs – use a very
special, large diameter, direct-drive
motor. These can be removed, complete with the stainless-steel shaft and
bearings, and then used as a wind generator, water generator, or even brushless DC motor.
We described how to convert one
of those motors to a generator for a
windmill in the January 2005 issue
(siliconchip.au/Series/84), and how to
use one as a motor in February 2012
(siliconchip.au/Article/766). Even if
you decide you don’t want it, these
motors are worth money second hand.
The electric pump from a washing
machine is usually quiet, relatively
low power (30~40W), can handle hot
Metric stainless-steel cap-screws
salvaged from a coffee machine. You
pay real money for stainless steel
fasteners like these, but here they
were free.
A microswitch, two normally open
temperature switches (107°C) and a
DPDT mains relay rated at no less
than 16A, all hidden in a discarded
coffee machine.
worth salvaging; they are heavy duty
with typical ratings of 16A at 250V AC.
Cautions
When you’re pulling apart a photocopier, you need to be careful of a few
things. Disassemble the copier outside
while wearing old clothes – inevitably,
toner will get everywhere.
Some copiers use torsion bar springs
to counterbalance the weight of the
open top half; these springs are very
powerful and if you undo their retaining screws while they’re under tension, they can fly out.
Other copiers use small gas struts –
another excellent salvage part.
The high-voltage power supplies
have onboard capacitors that could
give a nasty bite – they’ll be fine if
the copier hasn’t been powered-up
recently, but keep the potential in
Inside discarded coffee machines
you’ll find a very special pump. An
AC design that oscillates at mains
frequency, the pump produces very
high pressure (over 15bar) and is safe
to use with water.
56
Silicon Chip
Australia's electronics magazine
siliconchip.com.au
If you can get them for nothing, washing machines are well worth pulling apart for their components. The water-control
solenoids from washing machines are worth salvaging, especially if they’re 12V designs. Like the one shown at upper
right, however, most are mains-powered. These LEDs, pushbutton switches and the rotary encoder were salvaged from
the control panels of just two washing machines. All washing machines contain mains-powered pumps as shown at lower
right. They’re quiet, use little power, can handle hot water and have removable filters.
water and has a removable lint filter.
These characteristics make the pumps
excellent for circulating water in a
solar water heater or for low pressure
water transfer.
However, if using a pump in this
way, always ensure the wiring is
appropriately insulated and Earthed
and that water cannot come in contact with it.
There are two (sometimes three)
solenoids in each washing machine.
These are electrically operated valves
that control water flow. Most washing
machines use mains-powered solenoids, but some use 12V solenoids.
The solenoids can be used whenever mains-pressure (or lower) water
supply needs to be switched on and
off. The lower-voltage solenoids can
be easily and safely used to control
siliconchip.com.au
water flow in a variety of applications,
including solar water heating systems,
gardening or recreational vehicles.
They will cope with high water
pressures and are usually leak-proof.
The mains-powered solenoids should
be used only in insulated surroundings.
Old washing machines use a
mechanical pressure switch to detect
the water level. The water level adjustment is achieved by altering the spring
preload. These switches are simple to
use, high current, very sensitive and
are always worth salvaging. An example use is for warning of a low water
level in a rainwater tank.
More modern washing machines use
variable output electronic water level
sensors. That sounds good, but most
of these sensors appear to use an iron
Australia's electronics magazine
core moving within encapsulated electronics and I haven’t found an effective
way to interface with them.
Many washing machines now incorporate heater elements to allow higher
water temperatures than can be provided by the domestic water heater
(and/or to allow a single cold water
hose to be used).
These machines use a temperature
sensor to monitor the water. These sensors are excellent parts to grab, being of
stainless-steel construction and with
quite a quick reaction time. They use
an NTC thermistor, where the resistance falls as its temperature rises. As
such, they are suitable for temperature
sensing in a range of applications.
Most electronics in washing
machines is ‘potted’ – that is, the
boards are covered with a thick layer
July 2025 57
of rubbery plastic, waterproofing them.
It’s pretty well impossible to salvage
components from these boards.
However, the control panel is usually not potted. By placing the control panel board in a vice and using
the heat gun approach described earlier, it’s possible to salvage parts in
literally seconds. Parts likely to be
available include LEDs, switches and
rotary encoders.
There is a surprisingly large
amount of hardware in many washing
machines. Much of it is of high quality: stainless-steel self-tapping screws,
heavily plated machine screws, and –
in front-loaders – many long self-tapping hex-headed bolts (they hold the
drum halves together).
Because the washing machine tub
needs to cope with out-of-balance
loads, most machines also incorporate springs to allow tub lateral movement (top loaders) or vertical movement (front-loaders). These springs are
heavy-duty and a well worth salvaging. You’ll also find a variety of rubber
hoses and spring clips.
Finally, there’s usually plenty of
wire of different gauges and colours
– perfect whenever you need a short
length of hook-up wire.
Video cassette recorders
VCRs were once among the most
numerous of electronic consumer
goods being discarded. Now, they’re
becoming much rarer, but they do still
sometime pop up as giveaways. Contrary to what you might expect, the
best bits are mechanical rather than
electronic.
The pick of the bunch is the video
drum assembly – I am happy to pull
apart a VCR just for the video drum.
Why? It contains a precision-ground,
hardened steel shaft. It also uses two
precision sealed ball bearings that perfectly match the shaft.
You also have two light alloy housings, one of which is normally a press
fit on the shaft and the other that
houses the two bearings. Finally, there
is a brass collar with a grub screw that
fits perfectly on the shaft.
In almost any application where
you need small bearings and a shaft
Shown in the left photo is the rotating video head from a VCR. Even the cheapest VCR has a good-quality spinning
assembly, and in disassembling over 50 VCRs, I’ve yet to come across one with worn-out bearings. At right, the video
drum from a VCR contains precision matched components, including a hardened steel shaft, two bearings and two alloy
castings. The brass collar, complete with retaining grub screw, is a tight fit on the shaft.
Top: PCB-mounting RCA sockets
salvaged from a VCR.
Right: a sensitive wind vane that uses
the components from a video drum for
its rotating bearing.
58
Silicon Chip
Australia's electronics magazine
siliconchip.com.au
or axle (robotics, a wind vane, small
wind generator, model car etc) these
parts can be used. Furthermore, as
they’re pretty well standard across
all VHS VCRs; if you need two axles
(or four bearings etc), just keep collecting!
In addition to the video drum, inside
a VCR you’ll also typically find small
springs, switches, wire-wound resistors and RCA sockets. You will also
often find a DC brush-type permanent
magnet motor that uses a worm reduction drive to turn a slowly rotating
output shaft. It would make a perfect
winch for a model boat, or a merrygo-round for a model railway layout
or kids’ toy.
Cordless drills
If VCRs are now getting scarce, the
same can’t be said for cordless drills –
they seem to be thrown away in their
thousands every week.
At the tip, at garage sales, even in
kerbside rubbish pick-ups; there are
now always plenty of defective battery-powered electric drills. You might
even have one or more broken cordless drills tucked away at the back of
your workbench.
Cordless drills usually have a maximum speed of 1000RPM or even less.
To reduce the speed of the DC electric
motor, and to increase the torque, a
planetary gearbox is used. In fact, most
often there are two planetary gearsets
back-to-back – rather like the gear systems used in traditional automotive
automatic transmissions.
And like automotive transmissions,
some cordless drills let you select
between ratios – more on that in a
moment.
For their size, planetary gears are
very strong and, especially when
two sets are used, allow high reduction ratios to be achieved in small
volumes. Considering their size and
torque capacity, these are really nice
little gearboxes.
The torque multiplication might be
achieved by the gearbox, but if you
want to be able to quickly drill holes –
or screw screws – you need power. It’s
provided by a high-current DC brushed
motor. Brushless motors are now available in electric drills, but I haven’t seen
many yet on the discard pile.
Typical drill motors draw around
10A at 12V when stalled, and considering they are about the size of a
D cell, that’s a powerful motor you’ve
siliconchip.com.au
A discarded battery-powered drill contains a powerful low-voltage, brushed DC
electric motor and a compact but strong epicyclic gearbox. Many also contain a
PWM speed controller.
The epicyclic gearbox. Many drills use two geartrains mounted back-to-back,
while some allow two different gear ratios to be manually selected.
A brushed electric drill motor being driven by a crank placed in the chuck,
making a low-voltage hand-powered generator. Over 2.5W is easily available, so
a powerful LED can be driven, or via a 5V converter, a phone charged.
Australia's electronics magazine
July 2025 59
Top ten parts to salvage
We’ve been looking at the parts you
can salvage from specific pieces of
equipment, but you can turn the process around and look at the best parts
to get. Here are the top ten.
1. Knobs
Whenever you see a piece of equipment
with quality knobs on it, grab them! It
takes literally seconds to pull knobs off,
and it makes such a difference when
you’re building a project if you can just
go to your storage drawers and immediately lay your hands on a knob that’s
just perfect for the application.
It’s also interesting sorting through
different knobs and feeling the way in
which they work – some knobs (eg,
amplifier volume controls) need to be
large and smoothly contoured; others
(like the adjustment knob on an electronic thermostat) need to be small
and much better shaped to suit fine
adjustment.
2. Switches
A switch is one type of electronic component that doesn’t go out of date.
Over the years, I’ve collected switches
from:
∎ VCRs (miniature pushbuttons,
microswitches and the contactless Hall
Effect switches often used on the video
drum chassis)
∎ photocopiers (the switch that
deactivates the power when the lid is
raised)
∎ old electric typewriters (typically,
the main on/off switch is a quality pushfit rocker design)
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Silicon Chip
∎ amplifier input selectors (a multipole rotary switch)
∎ old washing machines (the water
level switch – a very sensitive pressure switch)
∎ miscellaneous heavy duty equipment (high-current switches)
All are useful and, even better, easy
to use.
3. Cable clamps, mounts and holders
Whenever you run wires or cables
around inside a piece of equipment,
there’s a need to hold them in place.
Inside commercial equipment, you’ll find
the full gamut of cable and wire holders
– bendy insulated metal strips, steel
clamps, plastic clamps, clamps that pop
into chassis holes and clamps that hold
mains-power cables. It’s always worth
collecting these.
4. Fuses
Fuses are another example of a component that doesn’t date – a 50-year-old
glass fuse and holder are just as useful
today as back then.
As a matter of course, I collect fuses
from all sorts of equipment. If the fuse
holder is inline or an easily removed
chassis-mount design, I collect those
too.
You can also obtain very useful fusible links from car fuse and relay boxes,
and much industrial equipment contains
resettable circuit breakers.
I also collect the two different sizes
of blade fuse used in vehicles. It is not
at all hard to collect enough fuses that
you’ll never need to buy one again – or
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spend the time travelling to the shop to
buy that required obscure value.
5. Relays
Relays are extraordinarily useful –
rugged (basically impossible to blow
up unless you do something really
stupid!), universal within voltage and
current restraints, and easy to wire
up. An enormous range of equipment
and appliances have relays inside –
you can easily collect one from every
even moderately complex bit of gear
you salvage.
Commercial equipment often uses
solid-state relays, and I remember picking up the ABS (anti-lock braking) controller from a car and realising with joy
that it contained no less than six small
high-current 12V relays!
6. LEDs
The idea of salvaging LEDs from equipment can seem silly – why bother when
LEDs are so cheap new?
First, it’s easy to salvage LEDs you
cannot readily buy in shops – those
with odd lens shapes (eg, long rectangular types) and LEDs with unusual
colours.
Second, using the heat-gun-and-
pliers approach mentioned above, it
takes almost no time to salvage dozens
of LEDs. I often use shop-bought LEDs
in projects, but nearly as frequently,
I’ll want something out of the ordinary
and reach for my little drawers of salvaged LEDs.
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I come across – they’re amongst my
‘most-utilised’ salvaged parts.
7. Plugs & sockets
If you’re trying to find the right plug for
a socket (eg, a DC socket that requires
the correct mains adaptor), a visit to an
electronics supplier is often required.
If, on the other hand, you’re building a
piece of equipment and need a similar function low voltage DC plug-andsocket combination, it’s often much
easier and cheaper to use some that
you’ve salvaged.
For example, I often use RCA-style
plugs as low-voltage DC power connections – they’re polarised, non-shorting
and can handle reasonable current.
You can salvage RCA sockets from any
audio or video consumer item that’s
been thrown away. The plugs are almost
as often discarded on audio interlink
cables!
8. Heatsinks
Heatsinks are available in discarded
goods in a huge range of sizes – from
small ‘tab’ style ones in power supplies to large heatsinks in audio amplifiers, and every size in between. When
building projects, it pays to have a
large variety of heatsinks on hand.
That’s because there is often not only
a requirement for heat handling but
also physical requirements as to size
and shape.
For example, space might be tight
in one direction, or the flat mounting
surface on which the components are
to be mounted might need to be a certain shape. I collect all heatsinks that
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9. Small motors
Many items that people throw away
contain electric motors. Bread makers
use mains-powered universal brushedtype electric motors; electric typewriters, printers and fax machines use
stepper motors; and VCRs contain
small low-voltage brushed motors.
And as we’ve seen, washing machines
and other larger goods contain mains-
powered induction motors.
I tend to collect just the following motors types: small low-voltage
brushed motors (good for making fans
and kids’ toys), and large and small stepper motors (good for robots, model railways and hand-cranked generator projects). Motors (of any sort) that can be
removed complete with reduction geartrains are always useful.
10. Fans
Cooling fans inside discarded equipment come in all shapes and sizes.
PC-style fans can be found in PCs (yes,
really!) and photocopiers. Fans with
removable blades can be salvaged from
microwave ovens, but open a microwave
only if you know exactly what you are
doing – they can be very dangerous.
Squirrel-cage fans are used in much
industrial equipment, as well as some
types of domestic heaters. Fans are
typically either mains-powered or run
from 12V or 24V DC. Considering
the cost of new fans (especially large
ones), real savings can be made in
this area.
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got your hands on – especially since
it cost nothing!
Many cordless drills have an
electronic variable speed function,
achieved by pulse-width modulating the power feed to the motor. The
switching transistor is mounted on a
separate interior heatsink and the rest
of the control electronics are integrated
with the trigger switch. A reversing
switch is often mounted directly above
the speed control.
Even if you grab just this bit, you
have a high-current, low-voltage electric motor speed control (or light dimmer etc). Finally, most of these drills
have an adjustable slipping clutch that
allows the peak torque to be set before
drive ceases.
There are plenty of uses for these
bits and pieces. One of the easiest is
to simply pull the body of the drill
apart (because they are low voltage
devices, tamper-proof screws aren’t
fitted, making it really easy) and cut
the wires at the motor. Bend a piece of
steel rod into a crank-shaped handle
and lock one end in the chuck. Turn
the handle and you have a powerful
small DC electric generator.
How powerful? On one unit I measured, it was quite easy to run a halfamp load at 5V – that’s 2.5W. 2.5W is
plenty to run high efficiency power
LEDs, or even work through a 5V regulator to charge a phone.
If you pick a drill that has two
user-selectable gear ratios, it works
even better. In one ratio, turning the
handle is easy, but the amount of
power generated is lower. Or, you can
slide over the gear selection lever and
have around twice the power output
at the same rotational speed – but, of
course, it will be much harder to turn
the handle.
The motor/gearbox/clutch/chuck
assembly can also be used wherever
a high torque output, low-voltage
mechanical drive is needed. For example, two of the assemblies can easily be combined to form the individual wheel traction motors for a small
robot (or use four for the ultimate in
manoeuvrability!).
Alternatively, the assembly can be
used as a small winch, eg, to hoist a
model railway baseboard up near the
ceiling when it isn’t being used. In
these applications, the built-in slipping clutch is a real asset, as it stops
the motor from being overloaded when
SC
the output is stalled.
July 2025 61
Hot Water System
Solar Diverter
Part 2 by Ray Berkelmans
& John Clarke
Solar-optimised hot water system (HWS)
heating using power purely from excess
solar generation
Solar export data is obtained from the
inverter and updated every five seconds
Shows operational parameters on a 2.4inch OLED screen
WiFi logging of operational parameters
to a ThingSpeak database every five
minutes
Automatic override if the HWS
temperature is still cold by the end of
the solar day
Night-time power-down
Active heatsink cooling
Email alert (one per day) if
communication with the inverter is
lost
Over-the-air program updates via
WiFi
Manual override switch
This HWS Solar Diverter,
introduced last month, monitors the
solar power available from a PV array and controls
the hot water system to maximise the use of power that can’t be exported.
It’s a lot less expensive to build than commercial equivalents. We’ll finish
Background Image:
construction, then get into setup and testing.
unsplash.com/photos/sunset-view-5YWf-5hyZcw
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siliconchip.com.au
T
he first article last month explained
how the Solar Diverter works and
also provided the parts list and
the majority of the PCB assembly
instructions. At this stage, we have a
mostly complete PCB, ready to install
in the enclosure. There are still a few
parts to fit, and some wiring to be done,
before we can get to the testing and
calibration stages.
Enclosure cutouts
Holes are required in the enclosure
for the fan exhaust, air entry, PCB
standoffs, one for the cable gland plus
those for the conduit glands. Fig.4
shows the shapes of the fan cutout
and mounting holes, plus the series of
air entry holes required on the opposite end of the heatsink to allow air to
enter and pass through the enclosure
with fan assistance.
The fan mounts unconventionally
because the lid’s internal flange is
thicker than the enclosure base. As a
result, two of its mounting holes are on
the lid and two are in the base. Thus,
the circular cutout for the fan is made
with the lid attached to the base, but
without the Neoprene seal fitted.
The hole can be made using a
series of small (3mm) holes around
the inside perimeter and then filed
to shape. The difference in thickness
is about that of an M3 nut and so the
bottom screws for the fan simply pass
through the lower mounting holes of
the fan with a nut on each screw tightening to the inside base of the enclosure. They do not secure the fan but
locate it in position.
It is the top two screws that secure
the fan to the lid once it is positioned
on the base. To make this practical, the
nuts need to be attached to the rear of
the fan inline with the two top mounting holes. This can be done by gluing
them to the back of the top two fan
mounting holes using silicone sealant
or epoxy resin.
Alternatively, the nuts can be
adhered by heating the nuts with a
soldering iron sufficient to just melt
the nuts into the fan plastic.
It is not necessary to use a fan guard
to protect against cutting fingers on
the rotating fan blades, as the fan isn’t
sufficiently powerful to cause injury.
Heatsink temperature sensor
Temperature sensor TS1 is held
against the fin of the heatsink using a
transistor mount clamp and secured
with an M3 screw. You will need to
drill a hole through the fins to gain
access to the head of this screw. Make
it large enough to allow a No.2 Phillips
screwdriver to be inserted to tighten
or loosen the securing screw.
It is important that the heatsink is
mounted so it is not too close to the
leads of IC1 or the Triac. The minimum clearance is 6mm. The PCB
screen printing shows the position
for the heatsink, with a 45° diagonal cut at the lower right of the
heatsink mounting flange. This may
be required to provide clearance
Fig.4: the cut-outs and
holes required in the
case. The rectangular
cut-out in the lid is
larger than the OLED
screen but a bezel
covers everything
except the visible area.
Note how the fan hole
spans the lid and base;
you need to clamp
them together, without
the waterproof sealing
strip, before marking
and cutting the hole.
Warning: Mains Voltage
This Solar Diverter operates directly
from the 230V AC mains supply; contact
with any live component is potentially
lethal. Do not build it unless you are
experienced working with mains
voltages. A licenced electrician is also
required to install the project.
Do not power the PCB from AC mains
while the serial cable is plugged into
the PCB. Doing so is unsafe and could
destroy the USB port on your computer,
the computer and/or the Solar Diverter.
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July 2025 63
between the heatsink & IC1’s current-
carrying lead.
The PCB screen printing also shows
the positions for the heatsink’s lefthand mounting screws, the right-hand
mounting screws (used in conjunction
with IC1’s shield as described below),
the Triac mounting hole and the heatsink Earth screw position.
The top side of the heatsink surrounding the Earth hole needs to have
the anodised coating scraped away to
ensure the Earth lugs make good electrical contact with the heatsink.
The Earth screw inserts from the
underside of the PCB through the heatsink and is secured using a star washer
and M4 nut. The Earth lugs mount over
this and are secured with another star
washer and another M4 nut.
Insulating shields
Three shields are used to cover
exposed mains connections on the
PCB, for OPTO1, IC1 and the mains
input section. They are mounted on
M3 tapped spacers. They could be
made from fibreglass (eg, FR4) but we
decided to use clear or translucent
laser-cut acrylic as you can see through
it. These laser-cut pieces, shown in
Fig.5, will be available from our Online
Shop, along with the PCB.
The shield mounting for OPTO1 is
straightforward, using 6.3mm spacers
that are secured with 5mm-long M3
screws from the underside and similar
screws plus washers on top.
IC1’s shield is also pretty simple as
it only has two mounting holes, both
of which are held in place by the same
screws used to attach the right-hand
side of the heatsink to the PCB, with
washers under the 15mm-long M3
screw heads and nuts between the
shield and heatsink. Those screws are
secured with two more M3 hex nuts
on the underside of the PCB.
The mains wiring shield is the largest one and uses 3mm-thick acrylic
(the other two can be thinner, eg,
1.5mm or 2mm). We use 12mm-long
screws from the underside to secure
6.3mm spacers to the PCB, then 12mm
spacers are added onto the exposed
screw threads. The shield is then
held to the top of the 18.3mm (6.3mm
+ 12mm) spacers using M3 × 5mm
machine screws through the top.
Test-fit this, then remove it until the
mains wiring is complete (see below).
Low-voltage wiring
The two DS18B20 temperature sensors need to be wired to connectors
CON5 and CON6 for sensing the heatsink and water system temperatures,
respectively. Both sensors are wired to
plugs that plug into these two headers. The wiring lengths need to be sufficient to reach the heatsink (for TS1)
and the water heater (for TS2) via the
cable gland.
Use heatshrink tubing around the
DS18B20 leads to prevent them from
shorting to anything.
The LDR wiring also passes through
the cable gland so the LDR itself is
outside of the enclosure and thus can
sense the ambient light level. Connections also need to be made for the fan
power, to CON4. Make sure the fan’s
red wire goes to the pin marked + on
the PCB.
The OLED screen also needs to be
wired to a plug that fits into CON1.
Take care with the pinout or you
could damage the screen and note that
some screens may have SCL and SDA
swapped, or even VCC and GND! So
Fig.5: the OLED bezel and shields. These will be available as a set, along with
the PCB, pre-cut to the required shapes. The OLED bezel should be opaque (eg,
black) while the others can be transparent or translucent. The mains wiring
shield is made from thicker material as it is larger and thus needs to be stronger.
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you will need to check carefully and
adjust the wiring to get the right signals to the right pins of the connector
(they are labelled on the PCB). SCL is
the clock signal for the OLED screen,
while SDA is the data line.
Display and bezel
The display is mounted within a
cutout in the enclosure’s lid, as per
Fig.4. But note that this is to suit the
particular OLED screen we used; they
can vary in dimensions slightly, so
check yours before cutting the hole.
A front bezel covers everything except
the OLED display area. The bezel
dimensions are in Fig.5.
Mains wiring
The Solder Diverter needs fixed
mains wiring, so you will have to get a
licenced electrician to wire it between
your water heater and its mains supply. We suggest you test it thoroughly
and make sure everything is working
(as much as you can test) before taking this step.
First, run a 2.5mm2 red mains-rated
wire between the A1 terminal of CON7
and the IP- terminal for CON8.
The input and output wires should
use mains-rated 2.5mm2 flat twin
and Earth cable, with similar wiring for switch S2. S2 is the bypass
switch, a 20A mains-rated switch in
an IP66 housing. The wiring should be
run within 20mm or 25mm conduit.
Secure the shield over this wiring once
the connections have been made.
Software setup
We will log our data to an online
repository and graphing service called
ThingSpeak (see Screen 1). If you don’t
already have an account, navigate to
https://thingspeak.com and open a
free account. You can then set up one
of your allocated channels with up to
eight fields, as detailed in our September 2017 article on the Arduino
ThingSpeak.com ESP8266 data logger by Bera Somnath (siliconchip.au/
Article/10804).
We only need four fields for our data,
and you can set them up as follows:
• Field 1: HWS temperature
• Field 2: H’sink temperature
• Field 3: Excess solar
• Field 4: HWS heating
Note the “Write API key” on the
ThingSpeak.com website, as you will
need to include it in your Arduino
sketch.
siliconchip.com.au
Screen 1:
an example
of the data
that will be
available on
ThingSpeak
after the
HWS Solar
Diverter
has been
running for
a few days.
We will also send ourselves an alert
email if the solar diverter fails to connect to the inverter for longer than 15
minutes. Otherwise, if the inverter
cannot be reached, we may end up
with a cold shower!
For this, we will use a free email
service called PushingBox (www.
pushingbox.com). There is no need to
open an account if you already have a
Google account.
Once you log in, you will be taken
to the Dashboard screen, where you
will see an email “Service” already
configured for you. You can edit this
if you need to. From here, you need
to create a “Scenario”, which will
action our email alert.
You could name it “Solar
diverter status”. Enter a Subject (eg, “Solar Diverter”)
and an email Body (eg, “The solar
diverter cannot connect to the inverter.
Time to check it out!”). That is it! Note
the DeviceID key, which we will use
in our Arduino sketches.
You need the Arduino IDE installed
with the ESP8266 Boards Manager to
program the ESP8266 module. For
details on how to do this, refer to the
Silicon Chip article mentioned above,
or Tim Blythman’s article on “The
‘Clayton’s’ GPS Time Source” in the
April 2018 issue. The Arduino IDE is a free
Heatshrink tubing should be used
around the leads of the LDR (lightdependant resistor, above) and the
DS18B20 temperature sensor (below).
The side
shot of the
case shows the cutout
required for the 40mm fan.
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download from www.arduino.cc/en/
software
The main program file for the solar
diverter is “Solar_diverter_HWS_1reg.
ino” or “Solar_diverter_HWS_2regs.
ino”, depending on whether your
inverter stores its export data in one
or two registers. These sketches can
be downloaded from siliconchip.au/
Shop/6/1835
First testing step
There are quite a few elements to
this sketch, which has over 600 lines of
code, so it is worth testing and validating the software and hardware in parts.
This helps in fault-finding/
debugging but will
also promote
understanding
of the code.
July 2025 65
Screen 2: these are some of the
messages you may see on the
Arduino Serial Monitor when
running the “Test_ping_alarm_
Pushingbox_NTP.ino” test sketch.
The first part to test is the Modbus
communication with your router, as
well as reading the temperature sensors and displaying the results on the
OLED screen. The test sketch is called
“Test_Modbus_temp_display_1reg.
ino”.
You will need to first install the
“Modbus-esp8266” library by Alexander Emelianov for this to work. You
also need the “OneWire” library by
Paul Stoffregen, the “DallasTemperature” library by Miles Burton and the
“U8g2” library by Oliver for the OLED
screen. All are available through the
Arduino Library Manager.
Edit the sketch to include your WiFi
credentials, as well as the IP address
of your inverter, port number and the
register address for your data previously determined using the “Modbus
Poll” program. There is a separate
test program called “Test_Modbus_
temp_display_2regs.ino” if you have
an inverter that holds its export data
in two registers.
To program the raw ESP8266 chip,
select the board type as “Generic
ESP8266 Module” and attach a USBto-serial converter to the PROG header
on the PCB, with Rx of the serial converter connected to the Tx pin on the
PCB, and the serial converter Tx pin
to the PCB Rx pin. You also need to
put a jumper on JP1 because the ESP
needs the IO0 pin held LOW to put it
in programming mode.
Power the PCB from a 5V DC power
source connected to CON3, being very
careful to wire it up with the correct
polarity. There is no reverse polarity protection! A 3.7V Li-ion battery will suffice for this, although a
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Silicon Chip
current-limited bench supply would
be better. Don’t be tempted to power
it from the mains just yet!
With the board powered up, press
tactile switch S1 to boot the ESP in
programming mode. You will see a
short blink of the blue on-board LED
as it boots. Ensure both temperature
sensors are plugged in and upload the
code. Once the code is uploaded, open
the Arduino Serial Monitor, remove
the jumper from JP1 and press S1
again. This runs the sketch.
You should see the display light up
with “Connecting to WiFi...”, followed
by “Connected to <IP Address>” once
connected. You should then see the
HWS and heatsink temperatures on
the screen, as well as the solar power
you are currently exporting or importing.
If you don’t see anything on the
screen, check the wiring on the display and the JST connector. If these
appear OK, it is worth installing one
of the I2C scanner libraries through
the Arduino Library Manager to see
if both the OLED and the ADS1115
ADC addresses can be found. The
OLED should be found at 0x3C, and
the ADC at 0x48.
If either is missing, check for solder bridges and trace-test your connections.
If you see the ESP log into your WiFi
but then reboot immediately afterwards, check that both temperature
sensors are plugged in. If so, check the
wiring at the temperature sensor end
and the JST connector end.
If it seems to work, switch a load on
in your house (eg, an electric jug/kettle) and verify that your solar export
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drops dramatically. Conversely, your
import power will increase dramatically. Hold your hand on each of the
temperature sensors in turn, and work
out which is which.
If the heatsink and HWS temperature sensors are the wrong way around,
change the line of code in the getTemps
function from: “DS18B20.getTempCByIndex(0)” to “DS18B20.getTempCByIndex(1)” and vice versa for the
second sensor. Physically swapping
the sensors between sockets won’t do
it as they are distinguished by their
fixed internal IDs.
Second testing step
For the next test, use the sketch
named “Test_ping_alarm_Pushingbox_NTP.ino”. This will ping your
inverter IP address and, if there is no
response after three tries, it will send
a message to PushingBox, which will
send an email alert to you.
It will also query a Network Time
Protocol (NTP) server to fetch the current time. We need this in our main
sketch to override the solar diverter
when solar conditions are poor and
when the HWS is below 50°C after
3:30pm. Full power will then be provided to the HWS for 2.5 hours.
Those parameters can be adjusted to
suit your needs, of course, but it has
worked well for us.
Aside from the standard Arduino libraries, you also need to install
“NTPClient” by Fabrice Weinberg, the
“Time” library by Paul Stoffregen, and
the “ESP8266-ping” library by Alessio Leoncini, for pinging the inverter.
Edit this sketch to include your WiFi
credentials, your PushingBox Device
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ID and your inverter LAN IP address,
then upload it.
In the Arduino Serial Monitor, you
will see if the ping is successful or
not. It will also show the alarm count
and whether an alarm message has
been sent (see Screen 2). Hopefully,
the pings are all successful so far. If
not, check that you have the right IP
address for your inverter.
Assuming the pings were all successful, try changing the inverter IP
address in the sketch to something
that is definitely not listed in the
client device list of your router and
re-upload the sketch. Now watch the
unsuccessful pings in the serial monitor. The alarm count should increase
to three before an alarm message is
sent via PushingBox. Check that you
receive the email.
After that, cut power to the unit to
avoid many alarm messages arriving.
In the main Solar Diverter sketch,
there is a flag that is set once an alarm
message is sent, and this is only
cleared on power up (or after waking
from sleep), effectively limiting the
messages to one per day.
At this point, it is advisable to log
into your router and change the LAN IP
address of your inverter from dynamic
(DHCP) to “Fixed”. We don’t want this
to change each time the inverter starts
up or our pings will fail incorrectly.
can get it). For example, if the offset
variable in software is 0.18 and the
current reading with no load attached
is 0.45A, add 0.45 to the offset variable, making it 0.63 (0.18 + 0.45).
In the Arduino IDE under Tools →
Port, you will now see a network port
named something like “SolarDiverter
at 192.168.50.180 (Generic ESP8266
Module)”. If you select this network
port, you can perform sketch updates
(upload) over the air (OTA). Try sending your updated sketch OTA. Note
that you will no longer have access
to the serial monitor output.
Testing the mains switching
Assuming the OTA upload worked,
you are now ready to connect some
wiring to test
boiling a jug of water. First, double-
check your existing wiring and the
component orientation on the board.
Place the PCB inside the enclosure
and secure it with machine screws.
Make sure the DC power source is
removed and the serial cable is disconnected.
Find an extension cord you can
cut in half and use for temporary AC
mains input and output connections.
From the plug end (input), run the
Active wire (brown) to the free terminal on CON7, Neutral (blue) to one
terminal on CON9 and the Earth wire
(green/yellow striped) with a crimped
eyelet to the heatsink Earthing screw.
Do the same for the wires on the
socket end (output): Active (brown) to
the ACTIVE OUT terminal on CON8,
Third testing step
The third part of testing involves
checking the mains switching, current measurement and over-the-air
(OTA) programming features. If you
were powering the PCB by a battery
in the preceding parts, you will need
to change to a 5V DC source.
With the PCB powered from a 5V
DC source, measure the voltage at
the current sensing ADC (IC2) at test
point TP4. This voltage value is used
in our sketch to calculate the HWS current. Enter this value in the variable
“maxADCVolt” in the “Test_Accurrent_measurement_PWM_OTA.ino”
sketch, along with your WiFi credentials. Set the PWM duty cycle to 100%
and upload it.
Check the amperage output on the
serial monitor and the OLED screen,
and adjust the “offset” variable so that
the measured current with no load is
close to zero.
To do this, simply add or subtract
the amount necessary to bring the measured current to zero (or as close as you
siliconchip.com.au
This photo
shows the
finished HWS
Diverter in the
case without the larger
acrylic shield from Fig.5.
July 2025 67
Neutral (blue) to CON9 and Earth to
the same heatsink screw. Also check
that the 2.5mm2 red wire is running
from the A1 terminal on CON7 to the
IP– terminal on CON8.
Attach the enclosure lid, then plug
an electric jug filled with water into
the extension cord socket. Plug the
AC input plug into a GPO and switch
it on. You should see the display light
up with “Connecting to <YourSSID>”,
followed by the LAN IP address when
connected, and finally, the current
draw of your electric jug.
If there is a switch on the jug, activate it and watch the current shoot
up to 8.5A, or whatever the rating
of your jug is. If you have a current
clamp meter, you can calibrate the
display output by carefully exposing an Active or Neutral wire (with
the power off) and clamping the jaws
around the wire.
Adjust the “mVperAmp” variable to
roughly match the current displayed
on the clamp meter. The easiest way
to adjust it is to multiply the existing
value by the proportion necessary to
make it read the same as the reference
(clamp meter) current.
For example, if the mVperAmp variable in software is 48.5 and a water jug
being heated shows as 10.4A, but the
clamp meter measures it as 8.5A, you
would increase the mVperAmp variable to 59.3 (10.4 ÷ 8.5 × 48.5). Note
that a larger mVperAmp value will
reduce the current shown since it is
used in the equation denominator.
After making that change, re-upload
the sketch OTA and check that the
display roughly matches the clamp
meter reading.
Now adjust the “pc” variable in the
sketch to vary the PWM duty cycle percentage to a lower value and re-upload
the sketch OTA. Your jug current draw
should be reduced proportionally; the
jug will heat slower, and the light may
dim or flicker.
When the duty cycle is low (say
below 20%), the OLED will occasionally display zero for the current draw.
This is normal because it is actually
quite tricky to display a pulsing current value. If you glance at your clamp
meter, you will see that it is all over
the place. With a load of 8A and duty
cycle of, say, 25%, the current is delivered as 8A, 0A, 0A, 0A, 8A, 0A etc.
So, even though we are measuring
our current for a full two seconds (100
cycles), the chances of sampling a zero
is quite high at low duty cycles. There
is no way around it other than sampling for even longer, but that would
make our program update slower than
it already does. Since it is only for a
visual indication of current flowing to
the load, we think this is an acceptable
compromise.
Final testing
With it passing all tests so far, it is
time to upload the final sketch, which
is named “Solar_diverter_HWS_1reg.
ino” or “Solar_diverter_HWS_2regs.
ino”. Do this over the air.
The complete sketch integrates all
the components you have tested above
and adds a few more, such as sending the data to ThingSpeak every five
minutes, using the LDR to check for
daylight, the automatic override if the
The HWS Diverter mounted on to a wall with the acrylic cover to protect it from rain etc. A licensed electrician is
required to wire the Diverter up, so make sure to properly test it before calling one in.
68
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siliconchip.com.au
water temperature is below 50°C at
3:30pm, and active heatsink cooling.
Before you upload the sketch, copy
your WiFi credentials and all the other
parameters you have used in testing to
it, including:
• your PushingBox DeviceID;
• the Modbus register and port;
• your inverter LAN IP address;
• your solar diverter LAN IP
address;
• your current measurement calibration details (mVperAmp, max
ADCVolt and offset).
You will also need to enter your
ThingSpeak API key and Channel
number.
Run this sketch for a while and
verify that all the components are
working, and that figures are being
uploaded to the ThingSpeak website.
If there is a hiccup somewhere, go
back to the relevant test sketch and
isolate the issue. Make sure you disconnect the AC mains and revert to a
5V DC power supply if you need to
poke around on the PCB.
Installation & commissioning
As mentioned earlier, you will
need a licensed electrician for the
final installation of the Solar Diverter.
This will involve fixing the enclosure
to the wall near the HWS. Since the
enclosure does not have any flanges,
you might like to make some using
two 100mm PVC square down-pipe
straps. Simply cut the middle (horizontal) section out and glue the sides
to the sides of the enclosure.
Alternatively, the enclosure has
wall-mounting holes in the corners
that are outside the weather seal, so
you can remove the lid, mark out the
four holes, drill them in the wall and
mount it using screws.
Talk to your electrician about adding
a 20A isolation switch near the enclosure. This makes it handy to de-power
or reboot the system. You can run the
HWS temp sensor to the PRT valve on
your HWS and add some extra lagging
for insulation.
Waterproofing
Assuming your enclosure and HWS
are not indoors but under the eaves of
your house, you should add an acrylic
cover as shown in the photo opposite. This will prevent driving rain
from entering the penetrations in your
enclosure. The cover is made from a
3mm-thick acrylic sheet, 340 × 307mm
siliconchip.com.au
Fig.6: if the Solar Diverter will be exposed to wind-driven rain (eg, under the
eaves of a house), it must be covered with something like this acrylic shield
to prevent water from entering the ventilation holes. Cut the acrylic sheet as
shown, then heat it to make the bends on a former like a piece of straight timber.
in size, cut and bent according to the
template in Fig.6.
You can bend the acrylic using a hot
air gun on maximum setting, moving
it continuously along the bend line.
It helps to clamp the piece to a sharp
edge to bend it over. Once the acrylic
is soft and starts to droop, use a piece
of timber to push the hot acrylic along
the bend line into position. Use outdoor silicone sealant to fill the gaps
in the joins.
Final calibration
Once it is all installed, you might
like to perform a final calibration of
the current sensor under the full load
of your HWS element. With power to
the HWS switched off, attach a clamp
meter around the Active at the HWS.
Power the system up and send a
sketch update OTA with the duty
cycle set to 100% and the time set to
your current time in the section near
the top of the Loop titled “// In case of
poor solar conditions”. Assuming your
HWS isn’t already up to temperature,
this will supply the full ~15A rated
power to the element.
Read off what your clamp meter
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reads and adjust the “mVperAmp”
variable in the sketch to suit. Re-
upload the sketch OTA and check
again. Once the current measurement
is reading correctly, reset the override
time in the sketch to 3:30pm or whatever time you’d like to have your HWS
heating on a poor solar day.
Conclusion
This circuit is essentially quite simple and comprises a WiFi-connected
microcontroller, two temperature sensors and the power control circuitry
(zero-crossing opto-isolator and Triac)
and not much more. The OLED screen,
current sensing and the ThingSpeak
data logging are nice add-ons but not
strictly necessary.
The secret sauce is in the software,
reading the exported power from the
inverter and using that to adjust the
mains-controlling PWM duty cycle.
There is also the email alert function
in case the inverter can’t be reached. If
you take your time and work through
the test sketches, we are sure you will
get to grips with the software very
quickly. Enjoy the savings from using
more of your own solar power!
SC
July 2025 69
Using Electronic Modules with Tim Blythman
8×16 LED
Matrix
These LED matrix panels
are bright, compact and
easy to drive, although
there are a couple of tricks to them.
After looking at the driver IC, we’ll provide demonstration software
for Arduino and BASIC code for the Micromite and PicoMite.
T
his LED matrix module was the
display and the base on which
we mounted the components for our
Digital Spirit Level project from the
November 2024 issue (siliconchip.au/
Article/17021).
We used Jaycar’s Cat XC3746 (www.
jaycar.com.au/p/XC3746), although
other modules with the same controller are available elsewhere. Our software should work with any of these
modules as long as they use the same
AIP1640 control chip.
In the Digital Spirit Level article,
we noted that the Matrix has pins
labelled SDA and SCL. While you
might think it would thus use an I2C
interface, that is not the case. So we
thought it would be helpful to delve
into the AIP1640 driver chip and the
communications protocol that it uses.
That will allow us to create software
to control the chip.
There isn’t much more to the module than the chip and its LED matrix.
The AIP1640 IC
The Wuxi I-core Electronics
AIP1640 is the main driver IC on the
module. Fig.1 shows the circuit of the
module, where IC1 is the AIP1640. It
comes in a 28-pin SOIC (small outline IC) package and 24 of its pins
connect to a matrix of 128 blue LEDs,
with eight anode drivers and 16 cathode drivers. It has an internal 450kHz
oscillator to control the multiplexing
of the output drivers.
Such an arrangement would be wellsuited to driving 16 common-cathode
70
Silicon Chip
seven-segment displays too. The only
other components are the standard
100nF supply bypass capacitor and
two 10kW pull-up resistors on the communication lines.
Unlike the Matrix module, the data
sheet labels the communication pins
as DIN and SCLK, hinting at the divergence from I2C. The power, ground,
DIN and SCLK lines are wired to a
locking four-way receptacle; a matching plug with wires comes with the
module.
This makes it easy to wire up to a
development board like an Arduino
Uno, since all the functions are controlled from the communication interface. You can download the data sheet
for the AIP1640 controller IC from
siliconchip.au/link/ac3e
Control interface
The data sheet includes sample
communication waveforms. Fig.2
shows this, along with a single byte
transmission in the I2C protocol. You
can see that the AIP1640’s protocol
resembles I2C, but it is not identical.
The idle state appears to have both
DIN and SCLK at a high level, like SDA
and SCL in I2C. The text describes the
lines being set low and high, whereas
I2C would have the lines set low and
allowed to rise to a high level through
the action of the pull-up resistors. It
seems that the start, stop and bit clocking restrictions are much the same
as I2C, although the AIP1640 only
expects eight, not nine bits.
A START condition occurs when
Australia's electronics magazine
DIN (or SDA) goes low, while SCLK
(or SCL) is high. During data transmission, DIN can only change state
when SCLK is low, while the END (or
STOP) condition is when DIN rises
while SCLK is high.
The AIP1640 sends the least significant bit (LSB) of the byte first,
while I2C sends the most significant
bit (MSB) first. The AIP1640 protocol
denotes the first byte as a command,
while I2C starts its transmissions with
an address byte.
The protocols are similar enough
that an I2C transmission could possibly be used to control an AIP1640 controller, but it would probably not allow
other I2C devices to coexist on the
same bus, since the I2C addresses may
clash with the AIP1640 commands.
Indeed, the AIP1640 has no concept
of addressing, so only a single unit can
be connected to a bus. Note that the
data sheet does not make any claims
to I2C compatibility; any confusion
appears to originate from sample code
that has been posted online.
Now that we’ve established that the
protocol is not I2C, we can examine
how to communicate with the chip.
The data sheet explains that some
commands are followed by data bytes.
Each command must be preceded by
a START condition, so the first byte is
a command and subsequent bytes in a
transmission are data.
Table 1 shows the commands that
the AIP1640 responds to. Each command is typically sent between a
START and END condition, except the
siliconchip.com.au
Fig.1: 128 blue LEDs are driven in matrix fashion by 16 cathode drivers and eight anode drivers in the chip, with all
timing controlled internally. Only two resistors and one capacitor are needed in addition to the AIP1640 driver IC.
Fig.2: the protocol used by the AIP1640 has a lot of parallels with I2C, but since it does not implement an addressing
scheme, it will not work on an I2C bus.
Set Column command, which would
be followed by data that is sent to the
display RAM for output.
Like many such devices, a small
siliconchip.com.au
amount of internal RAM stores the
display data and the host controller
can choose where in RAM it writes to.
There are 16 bytes, corresponding to
Australia's electronics magazine
the GRID1 to GRID16 cathode drivers.
Each bit corresponds with one of the
SEG1-SEG8 anode drivers, with SEG1
being the LSB and SEG8 the MSB. You
July 2025 71
Column 15
Bit 7
Bit 0
Column 0
Fig.3: the pixels are mapped logically, meaning it is quite intuitive to program the display. There is a column auto-increment
setting, so writing text from left to right can be accomplished easily. The back of the PCB is as sparse, with just the control IC
in an SMD SOIC-28 package, a few passive components and a four-way socket to suit the provided plug with leads.
can see the mapping of this to LEDs
on the XC3746 in Fig.3.
A typical display driver might send
a couple of commands to set up an initial state, after which pixels are written as needed to achieve the desired
display and display updates are sent
as required. A command might update
part of the display, or it might make
use of the auto-increment function and
send entire screenfuls of data at a time.
Power supply
The AIP1640 data sheet specifies a
5V±10% supply voltage, with input
voltage thresholds of 30% for a low
input and 70% for a high input. We
performed some tests with our Coin
Cell Emulator from December 2023
(siliconchip.au/Article/16039) and
found that our Matrix worked perfectly
well down to around 2.8V for its supply and logic levels.
With a 5V supply, the peak current
draw with all pixels lit was around
140mA. There are eight PWM settings
and thus brightness levels. We found
that a setting of 1 or 2 (0b001 or 0b010)
was adequate for indoor viewing.
Level 1 draws around 20mA with all
pixels lit, while level 2 draws around
40mA. The data sheet notes the different settings and their corresponding
fractions of the maximum duty cycle.
Unlike some controllers (eg, for
some OLEDs and LCDs), there is no
hardware register to flip or rotate the
display. For the Digital Spirit Level,
we had to invert the pixels and columns in software to have the connector
at the bottom of the display. You can
contrast that with the layout shown in
Fig.3, with the connector at the top.
driven by calls to the digitalWrite()
function, which all Arduino boards
and platforms support. We expect
you could use any Arduino board,
although we have not tried any others ourselves.
Arduino connections
PicoMite connections
Wiring the XC3746 up to an Arduino
Uno or similar board is easy enough
since there are just four wires. We
have written the software to be able
to use any digital pins. Fig.4 shows
the wiring with the default Arduino
sketch settings; if you change the connections, you will need to change the
driven pins by modifying the XC3746_
CLK and XC3746_DAT #defines in the
library file.
The “matrix” sketch uses the same
library we created for the Digital Spirit
Level, which provides simple functions to initialise and write to the display, including a simple font containing the digits 0-9. To use the library in
your own project, simply copy it to the
sketch folder and add the #include
directive.
The sketch lights up all pixels,
switches them off, then shows a rising count of elapsed seconds on the
display.
We used an Arduino Uno in our
examples, but there are no special
hardware features or other libraries
needed, so other Arduinos could be
used, like the Leonardo. The pins are
We’re using the PicoMite as our
exemplar BASIC platform since it is
easy to distribute a UF2 firmware file
that contains the BASIC environment
and code.
The firmware files can be loaded
onto the PicoMite without any special hardware using its USB flash
drive bootloader (accessed by holding
the BOOTSEL button while powering
on the PicoMite). All that needs to be
done is to copy the MATRIX.UF2 file
to the RPI-RP2 virtual drive.
The BASIC code should work on
other MMBasic platforms, such as
the Micromites, and we have also
included it in the software download.
You can load this directly using the
AUTOSAVE or XMODEM commands.
Fig.5 shows our wiring to the Pico
Mite. We used the 3.3V supply to
ensure there are no problems with the
logic levels from the I/O pins differing from the supply voltage. The 3.3V
regulator on the Pico can source up to
800mA, so it will have no trouble powering the Matrix.
We did notice a lower brightness
compared to using a 5V supply, with
brightness level 2 drawing only 4mA
with all pixels lit. That’s about a factor
of 10 difference compared to a 5V supply. Still, it seemed to work OK, and
there is scope to increase the brightness if needed.
You can change the pins used
by modifying the CONST values of
XC3746_DAT_PIN and XC3746_CLK_
PIN in the code. The BASIC program works the much the same as the
Arduino sketch, although it uses the
Table 1 – AIP1640 commands
Command
Action
Notes
0b0100bc00
Configuration
If b=0, auto-increment column
otherwise fixed
If c=1, activate test mode
0b10000000
Turn off display
0b10001ddd
Turn on display and
set duty cycle
ddd is three-bit duty cycle
(brightness) setting
0b1100eeee
Set column
eeee is 0 (GRID1) to 15 (GRID16)
72
Silicon Chip
Australia's electronics magazine
siliconchip.com.au
Fig.4: we used
the connections
here with our
example Arduino
sketch,
although
the data
and clock
pins can be
altered in the code
if necessary. The
XC3746 comes with
male jumper lead
ends that can be
plugged directly
into a board like
the Arduino Uno.
Fig.5: to interface
with a Pico (running
MMBasic), we used
the 3.3V supply to
ensure there was no
mismatch between the
supply voltage and I/O
pin logic levels. The
3.3V regulator on the
Pico can supply 800mA,
so it can easily drive the
display.
The XC3746
pack includes
the display
module and
a set of flying
jumper leads
equipped with
a plug, so it is
easy to wire
up. To connect
the Matrix
module to a
Pico, you can
solder socket
headers to its
pads or use a
breadboard.
The demo
software can
be downloaded
from
siliconchip.
com.au/
Shop/6/2756
internal PicoMite timer, so it might not
start counting from zero.
Note that the UF2 file will only work
with the original Pico and not the Pico
2. The BASIC code is compatible with
the Pico 2, but you’ll need to load the
latest version of MMBasic and then
the BASIC code yourself. If you see the
Pico’s LED flashing, that means BASIC
has been loaded correctly. So if the
Matrix is not working, but the Pico’s
LED is flashing, check your wiring.
Conclusion
These LED Matrix displays are simple enough to control, although you
might get tripped up if you try to use
example code that works with I2C,
since the interface is not the same.
They are great for small numerical
displays, as we have demonstrated.
Despite what the data sheet says,
our units seemed to operate happily
on 3.3V (which bodes well for many
modern microcontrollers). However, if
you want maximum brightness, a 5V
supply is the way to go; you may need
a level shifter if your microcontroller
has 3.3V I/Os. Perhaps the reason for
the specified narrow voltage range is
to provide a degree of uniformity to
the brightness.
With 128 pixels, these Matrix modules can display simple graphics or
other patterns. Jaycar sells the XC3746
Duinotech Arduino Compatible 8×16
LED Matrix Display for AU$19.95. SC
siliconchip.com.au
Australia's electronics magazine
July 2025 73
SSB Shortwave
Receiver
Part 2 by Charles
Kosina, VK3BAR
Introduced last
month, this new Shortwave
Receiver covers the entire shortwave
band from 3MHz to 30MHz. It is digitally tuned and
has a host of useful features like squelch, USB/LSB support, good
sensitivity (a -107dBm signal gives 13dB SNR), fast or slow AGC, an RSSI display and
it runs from 12V DC. This month, we describe how to build, test and align it.
T
his is not an overly difficult
device to build, as it uses no
tiny components or fine-pitch
ICs. However, it has two boards that
are fairly packed with SMDs plus quite
a few though-hole components, so you
should ideally have decent soldering
skills if you’re going to attempt it.
You also need some test equipment
to calibrate the Radio. That includes
an accurate frequency counter up to
100MHz and a signal generator that
will work up to at least 30MHz that
can produce a signal down to 10µV
or less (or an attenuator to allow that).
An oscilloscope with 100MHz or more
bandwidth is also nice to have, but not
absolutely necessary.
Some sheet metalwork is needed.
74
Silicon Chip
I recommend having a stepped drill
bit or two (eg, 3-12mm & 12-24mm)
on hand. A drill press would be ideal,
but you can do it with a hand drill if
necessary.
There are many components overall, but the values are marked on the
circuit boards to ease construction. It
pays to be careful as you go through
the assembly process and make sure
each part goes where it’s supposed
to. Mixing up two visually identical
capacitors could be enough to prevent
the radio from working.
Construction
Virtually all the components mount
on two PCBs, the Control Board
(Fig.14, 152.5 × 81.5mm) and the RF
Australia's electronics magazine
board (Fig.15, 152.5 × 51mm). There
are some through-hole components
used, but the vast majority are SMDs,
mostly passives (resistors and capacitors) in M2012/0805 packages, which
measure 2.0 × 1.2mm.
These passives are on the small side
if you are used to through-hole components, but we still consider them to be
in the ‘easier to handle’ category compared to really small parts. So as long
as you have the right tools, a decent
amount of light and reasonable vision
(or magnification), you should not find
the assembly too difficult.
Similarly, the ICs are not in really
tiny packages; they are mostly SOIC
types with 1.27mm lead pitch, ie, half
that of a through-hole chip. Again,
siliconchip.com.au
Fig.14: the
Control Board
has parts on both
sides; fit all the
SMDs first, then
the throughhole parts on
the underside.
The ICs, diodes,
electrolytic
capacitors and
the Arduino
Nano module
must all be
installed with the
polarities shown
here for the
Radio to work.
these are not what we would consider
difficult-to-solder parts.
Control board
I recommend building the Control
Board first and testing it before you
move on to the RF Board. There are
components on both sides of the board,
but most of the parts, including all the
SMDs, are on the front. Start by soldering the two ICs first, making sure
their orientations are correct.
In each case, find the pin 1 marker (a
dot or divot on the top, or a chamfered
edge on the side) and make sure it’s
aligned as shown in Fig.14 and on the
PCB silkscreen. It’s possible to solder
the pins of these SOIC package devices
individually with a fine-tip soldering
siliconchip.com.au
iron. Add plenty of flux paste to make
soldering easier and reduce the possibility of bridging pins with solder.
If that happens, use copper braid
with a bit of extra flux paste to remove
the excess solder. In fact, we usually
don’t bother trying to avoid bridges
as it’s so easy to clean them up later;
we’re more focused on making sure the
solder flows onto each pin and pad, to
avoid high-resistance connections that
can be difficult to find later.
Follow with the passives using a
similar technique. The resistors will
be marked with codes indicating their
values (eg, 10kW = 103 or 1002) while
the capacitors will not have any markings. In both cases, it’s best to unpack a
single value, then fit them all as shown
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on the overlay diagram so you can’t get
them mixed up. None of the passives
are polarised so they can be soldered
either way around.
Note that a few of these parts, like
the 68W resistor and 100μF capacitor,
are slightly larger than the others and
so have larger pads to suit. Also, two
of the 8.2kW resistors at centre left
are not fitted (marked R10 & R20 on
the PCB) as these are the I2C pull-ups
and the Si5351 module has onboard
pull-up resistors.
Follow by soldering the four identical Mosfets, which are all in three-pin
SOT-23 packages. The pins are small
but widely spaced, so this should not
be too difficult.
Don’t fit any of the through-hole
July 2025 75
components on the front side of the
PCB (where the SMDs have been soldered) yet. The Arduino Nano and
the Si5351 modules are on the back
of the board and can be plugged into
socket strips. This is important as if
either failed, replacing them would
be difficult.
15-pin socket strips are used for
the Nano and one seven-pin strip for
the Si5351. The only other parts on
the back of the board are the headers,
two electrolytic capacitors (which are
polarised, so make sure they’re fitted
the right way around) and the trimpot
for LCD contrast. All of those can be
mounted now.
As well as the speaker connector (CON4), there is another two-pin
header, CON3. This is connected in
parallel with the headphone jack
socket and may be wired to an RCA
socket on the back panel for an external powered loudspeaker.
Now go back to the front of the PCB
and fit the remaining through-hole
components. It’s important that the
switches, potentiometers and encoder
are square on to the board before soldering.
The way to ensure this is to attach
the black front panel with 16mm
tapped spacers to position these correctly; make sure that all controls turn
easily before soldering. For a better
appearance, rather than zinc-plated
screws, I used black 6mm machine
screws (which you can buy at Bunnings) to attach the front panel.
The jack socket is a unique part;
ensure it is pressed firmly on to the
board. Next, solder the 16-pin header
to the LCD module.
Don’t attach the LCD yet; clean the
board with de-fluxing solvent and
inspect all connections with a magnifier. Pay special attention to the solder joints on the socket strips for the
Nano, as they are not accessible once
the LCD is mounted. Before any modules are plugged in, use an ohmmeter
to ensure that there are no shorts from
the 12V or 5V supply lines to ground.
Finally, attach the LCD module using 5mm spacers and 12mm
machine screws and nuts. The Si5351a
module is held in place by 6mm M2
or M2.5 screws with 11mm threaded
spacers.
RF board assembly
If you want to take a break from
assembly now, you could skip down
to the “Programming the Nano”
sub-heading, complete initial testing
and calibration, then come back here
when you get to the part where you
need the RF board to be assembled.
The RF board overlay is shown in
Fig.15. Parts are only fitted to one side
of this board. As before, start with the
ICs (two NE612s, one LMC6482 and
the PCF8754) and ensure they are
all orientated correctly as you solder
them. All are in SOIC packages.
Then move on to transistors Q1-Q7;
Q7 is a Mosfet, while the others are
NPN RF transistors, but they all come
in the same packages, so don’t get them
mixed up.
Follow with Q8-Q10, which have
four pins since they are dual-gate
Mosfets. In all three cases, the wider
source lead goes towards lower right
with the PCB orientated as shown in
Fig.15. Fit diode D4 with its cathode
stripe as shown, then REG2 after first
applying a thin layer of flux paste to
its pads. That will assist in soldering
its tab properly. After that, solder the
SMD resistors & capacitors, noting that
the capacitors are again unpolarised,
and all the SMDs are on the board.
Mount the axial inductors next; they
have three different values, so make
sure the right ones go in each location.
They are not polarised, so you can fit
them in either orientation. Fit diodes
D2 & D3 next; they are polarised, so
ensure the cathode stripes both face
to the right. After that, solder RLY1 in
place with its pin 1 marking towards
the top.
Next, fit VC1-VC3, which are polarised in a sense, because we want the
adjustment screws to be connected to
the ground pins in each case. So orientate them as we have shown.
For the varicap diode, VD1, you
may get it in a two-lead TO-92 package like we did, or in an axial package, similar to a regular diode, which
can be mounted vertically. Regardless,
ensure its cathode lead goes to the pad
marked K; with the axial package, this
will be the end with the stripe.
Bend REG1’s leads down and attach
it to the board using an M3 machine
screw and nut, ensuring its three leads
go into their pads. Solder and then trim
the leads. Don’t do this before tightening the screw or you could fracture
the leads. I used a 16mm-long screw to
attach the tab as it makes a convenient
ground point for testing later.
Next, install CON1 and CON2. That
just leaves the crystal filter module,
XF1.
The crystal filter comes with SMA
sockets attached, and at least the input
one has to be removed. As it’s supplied, only the top connections are
soldered; I used a hot air wand to carefully heat them and slide them off, but
a soldering iron with a large tip could
also be used instead. Take great care
that other nearby components don’t
get removed as well.
Attach the filter to the PCB using
four 10mm-long M2 or M2.5 screws,
nuts and 5mm spacers. Solder wires
to connect the input and output of
the filter to the circuit board, one for
signal and another for ground at each
end. In theory, XF1 is not polarised,
but it’s a good idea to mount it like
we did, with the angled capacitor on
Fig.15: all the parts
are on the top side
of this RF Board.
Polarised components
to pay attention to
include the ICs, dualgate Mosfets, diodes,
relay and variable
capacitors. It’s best
to remove the SMA
connectors from the
crystal filter module
(XF1) before mounting
it on this board.
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the right-hand side, since that’s how
we tested it.
Toroid winding
The 3-10MHz toroid (T1) needs 42
turns of 0.35mm diameter enamelled
copper wire (ECW) for its secondary
and four turns of the same wire for
the primary. The secondary will take
a little while to wind; do it first and
neatly, with the turns almost touching
each other. There is just enough room
for that number of turns with a small
gap in between the ends.
Attaching the transformers to the
PCB is one of the most fiddly parts of
the assembly process. T1’s primary is
soldered between the pads labelled A
& B on the PCBs, and is wound near
the ‘cold’ end of the secondary, while
the secondary is soldered between
pads C & D.
I found it easier to attach the transformers to the PCB first, solder the
secondary windings, then add the primary windings. It is a bit tricky but I
think it is the best approach!
Make sure you scrape off the enamel
from the wire ends before soldering
them to pads A-D; otherwise, you
won’t get a good electrical connection
and the radio won’t work. It helps to
tin the ECW ends after scraping them;
if the solder won’t stick evenly, that
means you need to scrape off more
enamel first.
There’s also room for a tinned wire
loop to help hold the toroidal core to
the PCB at upper right. We recommend
you add this to prevent solder joints
from fracturing due to movement over
time. This does not form a shorted turn
as the pads it’s soldered to aren’t connected to anything.
The second toroid (T2) has 15 turns
of 0.6mm diameter ECW for the secondary, which you should distribute evenly. Make sure the direction
of winding is such that the ends go
into holes G & H in the PCB correctly.
Then add the two-turn primary using
0.35mm diameter ECW, scrape and tin
the ends and solder it to pads E & F.
Again, solder the piece of tinned wire
to hold it to the PCB.
Once all components have been
installed, give the board a thorough
clean to get rid of surplus flux. Inspect
all soldered joints and check for any
shorts with an ohmmeter. Make up
the connecting 16-wire cable with
IDC sockets.
Use a small vice or crimping tool to
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Wiring up the boards is pretty straightforward with a ribbon cable connecting
the control and RF boards. There’s room inside the enclosure to fit a three-cell
battery holder which can be used to power the Receiver.
evenly press the parts together; make
sure the cable is exactly square on to
the connector. Attach the loudspeaker
to the two wire connector and plug this
on the control board.
Programming the Nano
The Nano should be programmed
before it is plugged in. You can use
the free programming software called
AVRDUDESS for Windows that you
can download from siliconchip.au/
link/aaxh or use the command-line
version, avrdude, if you’re running
Linux or macOS.
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Connect the Nano via a USB cable
and check what COM port it appears
as. Select a baud rate of either 57,600
or 115,200 depending on the version of
the bootloader in your Nano. Select the
programmer Arduino for bootloader
using STK500v1 protocol from the
drop-down list; it may be the default.
Press the Detect button and it should
recognise the chip.
It is important that the programming
is done in exactly the following way,
making sure that the settings in AVRDUDESS are correct. Otherwise, you
could end up with a bricked Nano.
July 2025 77
There are two files to be loaded: the
program file, “SSB RX xx.HEX”, where
xx is the version, and the “SSB RX
xx.EEP” file, which is a binary file
loaded into the chip’s EEPROM.
There are five boxes below Options.
Tick “Disable Flash Erase”. Under the
Flash box, “Format” should be “Auto
(writing only)”.
Locate the HEX file to be loaded
into Flash by searching for it in the
square to the right of the Flash window. Locate the EEP file and place
in the EEPROM window. Select Raw
Binary from the drop-down list.
Tick the Write circle under Flash
and press the Go box. This will result
in progress messages in the bottom
window.
Tick the Write circle under the
EEPROM window and press the Go
box. It will also have messages in the
progress window.
This completes the programming,
and the Nano may be disconnected
from your computer and plugged into
the Control Board. Make sure its orientation is correct.
Initial testing
Connect power to the board via
CON1. Make sure polarity is correct;
if not, nothing will happen as there is
a protection diode. The LCD backlight
should be on, but there may not be any
text visible. Adjust trimpot VR6 until
you see text on the screen.
With the Band potentiometer
(VR3) fully anti-clockwise, the top
line should have 3.600.000MHz
and the bottom line USB or LSB,
depending on the position of switch
S2. There should be a cursor visible
under one of the digits. When the
shaft encoder is rotated, this number
should change.
Depending on the particular encoder
used, it may operate backwards. In that
case, bridge the two pads marked DIR
above the LCD to reverse the direction.
Switch the power off and on; the
screen will show “SSB Receiver” on
the top line and version number on
bottom line for two seconds. Toggle
the USB/LSB switch and see that it
changes on the screen.
Press the switch on the shaft encoder
and check that each press moves the
cursor to another position under the
frequency. It should allow adjustments
in 10Hz, 100Hz, 1kHz, 10kHz, 100kHz
and 1MHz steps.
The Band potentiometer is a convenient way to cycle through the most
common amateur radio bands. It sets a
frequency partway through each band
starting with 3.6MHz, then 7.1MHz,
10.0MHz, 14.1MHz, 21.1MHz and
28.1MHz. 10MHz is not actually in
a ham band, but it has WWV transmitting time and accurate frequency
information.
Using an oscilloscope and a frequency counter, check the outputs of
the Si5351 module. CLK2 is the BFO
and that should read 8999.6kHz or
8996.6kHz depending on the position
of the USB/LSB switch.
CLK0 should have a frequency that
is the sum of the currently tuned frequency plus the BFO frequency. The
accuracy of these depends entirely
on the 25MHz crystal attached to the
Si5351 module, so you may get slightly
different values. At this point, it is
advisable to perform calibration.
Calibration
To calibrate the set, you need to
measure the actual frequency of the
25MHz crystal on the Si5351 module. This procedure will calibrate the
short-term accuracy to within less
than 5Hz. Switch off the receiver,
then rotate the Band potentiometer
fully clockwise.
Switch it on and the top line on the
LCD will show “Calibration”; the bottom line will show the nominal crystal frequency of 25,000,000Hz. In this
mode, the frequency on OUT0 is set to
exactly 10MHz.
Fig.16: the recommended hole locations and sizes for the rear panel. A stepped drill bit makes drilling these
straightforward. As this is at actual size, you could copy or download and print it and use it as a template.
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Measure the frequency on OUT0
with an accurate frequency counter
and rotate the tuning knob, which
increments or decrements by 10Hz,
until the output is as close as possible to 10MHz. It’s possible to get to
within 1Hz. It may take many turns,
as the crystal could be out by more
than 10kHz.
Turn the Band potentiometer anti-
clockwise to leave calibration mode.
The new value for the 25MHz crystal overwrites the original value in
EEPROM loaded by the EEP file, and
will be read every time the power is
switched on.
This calibration needs to be done at
regular intervals as the crystal may age
and can also drift with temperature.
Case preparation
The modifications to the case
involve drilling four 3mm holes in
the base to attach the RF board, plus
numerous holes in the back panel for
the power socket, antenna connectors
and the loudspeaker.
I used the Jaycar AS3025 rectangular speaker, but just about any small
8W speaker will be suitable. You will
need to adjust the mounting hole
positions if using a different speaking, though.
Fig.16 shows the suggested hole pattern. I used a stepped drill bit, as they
make clean, circular holes. If you have
a drill press, that would be ideal, but
you can hand-drill these holes neatly
if you’re careful.
A word of warning! The drill can
grab the plate and spin it around, possibly injuring you, so for safety, always
make sure the plate is clamped firmly
while drilling the large holes.
Alignment
This should be done with the two
circuit boards not yet assembled into
the case to allow easier access to test
points. The only adjustments on the RF
board are the three variable capacitors,
and they should be peaked at 9MHz.
The way you do this depends on what
equipment you have.
Connect the control board to the RF
board with the flat cable and carefully
check that the two pin 1s are connected
together, ideally with the red striped
side of the cable to those pins (check
for continuity between the pin 1 pads
on the two PCBs). If you connect the
cable backwards at one end, you could
do damage!
Switch on the power and set the
frequency to, say, 7.1MHz or some
other convenient frequency. Use an
oscilloscope probe to check that you
have the VFO signal at about 16MHz
on TP3 and the 9MHz BFO on TP5.
Connect a signal generator to CON1
with the output set to about 100µV.
This is way above the lowest level,
but is useful for the initial setup procedure.
Tune the signal generator for a
whistle from the loudspeaker, which
should be very loud. Reduce the signal
generator output until you get some
background hiss from the speaker.
Adjust the antenna tuning potentiometer (VR1) for maximum signal, measure the DC voltage on TP6 and tweak
the three trimmers (VC1-VC3) for maximum output.
Fig.17: the front panel PCB overlay for the SSB Receiver. It is shown here at 70%
of actual size.
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That’s all there is to it; the receiver
should work across the whole range.
You will find as you tune across
10MHz, the relay will click to switch
between using T1 & T2.
Final assembly
The two boards and front panel can
now be assembled into the case. The
RF board uses M3 × 10mm threaded
spacers to attach to the bottom of the
case.
The antenna input connects via a
short ready-made cable between the
SMA connector to a BNC connector on
the back panel. Power is from a 2.1mm
or 2.5mm ID (inner diameter) DC jack
on the back panel to the two pin connector, CON1, on the Control Board.
The front panel attaches to the case
by four screws on the corners. Instead
of using the zinc-plated screws that
came with the case, I found some black
screws that look better.
All the rotary controls have 6mm
diameter shafts. It is preferable that
these have fluted shafts, as knobs for
these are more common. Still, there
are a few sellers on AliExpress that
have knobs with grub screws (they
are listed in the parts list last month).
Those were ideal for D-shaped shafts
but can also be used on fluted shafts.
Conclusion
Your Radio should now be operational and you can start scanning
the bands for signals! You can even
use it on the go, powered from a 12V
battery.
Note that while you could run this
radio from a 12V vehicle battery, you
must not do so (or connect it) while
the engine is running as it doesn’t
have protection from voltage spikes.
Unless you add a suitable filter, it’s
far safer to run it from its own interSC
nal battery.
When first running the Receiver
you must calibrate it by following
the text under the cross-heading
“Calibration”. This ensures accurate
timing.
July 2025 79
CIRCUIT NOTEBOOK
Interesting circuit ideas which we have checked but not built and tested. Contributions will be paid for at
standard rates. All submissions should include full name, address & phone number.
GPS Speedometer
The GPS FineSaver project (June
2019; siliconchip.au/Article/11673)
uses a GPS module to display the
instantaneous speed. It would typically be used in a vehicle as an accurate speedometer. In addition, it uses
the GPS system’s timekeeping to provide a clock feature.
It also has hardware to change the
volume of an audio signal based on
vehicle speed. We delved into why
this was a useful feature in that article.
A reader recently wanted to build
just the GPS speedometer component,
with the speed display as large as possible, making it easier to read.
Such a device could be built using
the same PCB as the FineSaver, but
with fewer components. It would
thus be less expensive and quicker to
assemble. The speed can be shown in a
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larger font since none of the other data
relating to other features or settings
would need to be displayed.
We investigated whether larger
OLED modules are available, since
that would be a straightforward change
and allow a larger speed display. There
are, but the ones that we found have a
different pinout or controller interface.
So they would require a new PCB or
driver to work.
Therefore, we opted to change the
firmware to work with a reduced component count. The cut-down version
of the circuit is shown here.
The parts needed include microcontroller IC1, its 100nF bypass capacitor,
the 10kW pullup resistor on pin 4, the
OLED screen (MOD1) and the GPS
module connected to CON7.
If you have a USB power supply,
mini-USB socket CON6 is sufficient
to provide 5V power. Otherwise,
D1, REG1 and the 10μF and 100μF
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capacitors can be used to obtain 5V
from a 9-12V input at CON1.
The firmware still allows the display
brightness to be adjusted. The parts
around CON5 (trimpot, resistor and
optional LDR) should be fitted if you
want brightness control; otherwise, a
jumper made from a component lead
offcut can be used to permanently set
the display to full brightness, as shown
by the dashed line.
We’ve changed the font so that it
uses the full 64-pixel height of the
OLED display without needing to be
upscaled. That makes it much easier
to read. The new font data ends up
using about half of the available flash
memory on the PIC16F1455 processor!
There are no user settings at all.
Instead, the choice of units is made at
compilation time, with kilometres per
hour (k), miles per hour (m) and knots
(n) being the available options. We
have created HEX files with the three
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options: 0110419K.HEX, 0110419M.
HEX and 0110419N.HEX.
The photo shows the assembled
PCB with the minimum parts fitted,
including a typical display showing
the speed in km/h. This has the fixed
full brightness modification.
If the GPS module is not fully operational and delivering valid speed
data, the status is shown by one, two
or three dashes. One dash indicates
that no data is being received, while
two dashes mean that data is being
received but the checksum is invalid.
That may mean an incorrect baud rate
setting. The FineSaver expects data at
9600 baud, which is fairly standard for
GPS modules.
Three dashes mean that the GPS
module is functional but has not
locked onto its satellites. You might
see this as the unit is starting up or
if you drive through a tunnel and the
GPS module loses its signal.
ICSP header CON4 is fitted to our
prototype. We used this during the
development of our firmware, but you
will not need it unless you plan to program your own chip.
You can use a PICkit 3, PICkit 4,
PICkit 5 or Snap programmer to work
with the PIC16F1455 chip.
The software, including source code
and the three HEX file firmware variants, is available to download from
siliconchip.au/Shop/6/1845
Tim Blythman,
Silicon Chip.
If the input falls below 1V, IC1a’s
output is high but IC1b’s output goes
low. In this state, segment d is driven
directly, while segments e & f are
again driven via D1 . This combination forms an “L” on the display. The
diodes serve to isolate the outputs of
the two comparators, ensuring they
don't interfere with each other when
sharing segment control.
A segment current of 3mA has
been selected to keep the total current within the LM393's maximum
sink current of 16mA. When displaying an “H” (which lights five
segments), the total current is about
15mA. Red LEDs are efficient and
should be bright enough at this level;
if using a different colour (eg, blue),
you may need to adjust the resistor
values accordingly.
The 10MW resistor biases the
input toward 2.5V when nothing
is connected, keeping the input
between the upper and lower thresholds so the display remains blank.
A 100kW series resistor protects the
comparator inputs in the event of
accidental overvoltage, working in
conjunction with the LM393’s internal ESD protection diodes.
The circuit can also be made
compatible with 3.3V logic levels
by changing the upper 1kW resistor
in the divider to 3.3kW. This shifts
the thresholds to approximately
2.7V (upper), 1.7V (bias) and 0.7V
(lower), aligning with standard 3.3V
logic ranges.
Circuit design by Silicon Chip,
Idea by Raj K. Gorkhali,
Hetadu, Nepal ($40).
Logic level indicator
This circuit displays an “H” on
the 7-segment display when the
input voltage is logic high, an “L”
when it is logic low, and nothing if
it is in between or left floating (high
impedance). It uses an LM393 dual
comparator, two diodes and a handful of passive components.
A string of four resistors (1kW,
1.5kW, 1.5kW, and 1kW) between
+5V and GND creates three reference voltages: 4V, 2.5V, and 1V. The
4V and 1V nodes are connected to
the non-inverting and inverting
inputs of comparators IC1a and IC1b,
respectively, while the input signal
is fed to their other inputs.
If the input signal is above 4V, the
output of IC1a goes low, sinking current through the b, c & g segments
via 1kW series current-limiting resistors. Since a red LED has a forward
voltage of around 2V, each segment
receives about (5V – 2V) ÷ 1kW =
3mA.
Segments e and f also light up
in this condition, as current flows
into pin 1 of IC1a via diode D2.
With segments b, c, e, f, & g illuminated, the display forms an “H”.
The series resistors for segments e
and f are chosen such that, despite
the additional voltage drop across
the diodes, they still receive close to
3mA for matched brightness.
siliconchip.com.au
Australia's electronics magazine
July 2025 81
SERVICEMAN’S LOG
Water woes and hydration hindrances
Dave Thompson
As a kid growing up in Christchurch in
the 1960s, we were always told that our
tap water was the best in the world. This
had been scientifically proven by men
in white lab coats many times over the
years, so it must have been true.
It certainly looked crystal clear and had no twigs or mud
(or worse) floating in it, so I had no reason to believe this
wasn’t the case. As it turns out, it was true. This was due
to the vast aquifers under the Canterbury plains, near to
the city. There was more than enough for everyone, which
included our relatively big city and many satellite suburbs,
along with all the nearby farmers’ requirements.
Many smaller towns in the locality all had their own
wells and supplies, and the world was rosy, and we all
loved each other.
Fast forward to 2010, and everything changed. We had a
series of huge earthquakes here; many people were killed
or injured in some of them. Three fault lines all went at
once – or within cooee of each other.
While the scientists at the university of Too Much Time
on Their Hands assured us the quakes were all unrelated,
I thought that just didn’t make sense. Why would three
faults, two of which were unknown at the time, all go off
at around the same time? It beggars belief.
We have been expecting “the big one” here for as long as
I can remember. New Zealand is positioned in the “ring of
fire” that stretches right around the Pacific Ocean, with a
series of volcanoes, above or below ground, causing almost
all of our seismic problems.
The Alpine Fault is where the Australian and New Zealand plates meet, close to our southern alps; it is likely why
those mountains formed in the first place. Geologists have
been telling us for years that this fault will go off again one
day, and it will likely devastate the country. Excellent!
An Earth-shattering kaboom
In September 2010, when I was almost thrown out of
bed by a huge ‘quake, I thought it had finally come. But no,
that quake was from a previously unknown fault just out
of town. It happened at 4:05am, and while it caused some
property damage and a few injuries – some major – it was
mainly just property. We all heaved a huge sigh of relief,
and rebuilding and normal life resumed.
The problem was that all our aquifers were very close to
where the fault burst, and this damaged them, so the water
quality suffered. Then, just a few months later, a much more
devastating ‘quake hit us from a different fault. It killed a
lot of people and injured many more, some very seriously.
It trashed entire suburbs, which will never be rebuilt. About
a third of the city was wiped out.
Buildings collapsed and facades fell, crushing people in
the street. This one had the highest lateral acceleration ever
measured in a ‘quake, likely because it was so shallow, and
even though the magnitude figure was lower than the 7.1 in
September the previous year, at 6.4, it was more devastating.
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This also affected the city’s water supply. Aquifers under
the city and reservoirs were cracked or destroyed, and corrupted by mud & debris. Many of the supply pipes also
broke. As a result, many people were without water; we all
suddenly had to rely on bottled water. Even worse, waste
systems were also destroyed, so we needed portable toilets.
I think every portable toilet and bottle of water in the
country was sent here. We had no power for a week, but we
did have gas, which we used to boil water for neighbours
who didn’t. It was the worst of times, but it often brought
out the best in people.
My usual long-story-short is that now our water was
not as good as it once was. Boil notices for tap water were
issued, and sales of water filters went through the roof, with
the local big-box store selling out in days. Many resorted
to using BBQs and whatever else they could fire up to get
clean water.
The supermarkets rationed milk, water & bread, and petrol stations rationed petrol and LPG, with kilometres-long
queues forming. The city water guys worked around the
clock to get pumping stations back online and repair the
infrastructure that had been ruined. In many suburbs, they
ran heavy polythene pipes along the footpaths to get water
to affected people.
The power companies did the same, laying overground
cables to get power to suburbs that were dark. It was an
interesting time to live.
Well, well, well
The upshot is that our water supply has never been the
same. A few years ago, the council decided to chlorinate
the water, to much wringing of hands and gnashing of teeth.
They claimed it would only be for six months, until they
could sort any contamination issues. Keep in mind this is
at least 14 years after the quakes.
It wasn’t long before the familiar chemical smell permeated our water. It may well have been clean, but it wasn’t
the water I grew up with. The first thing we did was install
an under-bench filter system so that, at least, our tap water
didn’t reek of chlorine.
A client of mine who worked for city water said that it
was temporary only while they sorted out the aquifers. Our
water is sourced from a 400m-deep well just a kilometre
from us, and it seemed fine before they added the chlorine
to it. I know I can’t analyse it, but it didn’t look or taste
any different. It turns out they did it to all water supplies
here ‘just in case’.
As I said, they claimed it was meant to be for a few
months. Now it’s a permanent thing, and the water is
disgusting, but only because of the chlorine, which they
promised we ‘wouldn’t even notice’. Hence the need for
filters. I’m not that happy about drinking chemicals every
day, and that’s aside from the ratepayers’ costs we have to
stump up for it year on year.
A faulty filter
Anyway, rant over. We have several water filtering
devices in our kitchen now because one just isn’t enough.
Under-bench filter systems are expensive to keep going, so
we have a couple of standalone filters.
One is a ceramic, two-part, bench-standing thing with
a stone and ceramic compound filter in the top half. We
pour water in that part and, at the rate of one litre per
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hour, it drips into the bottom tank, which has a tap. This
means we can draw clean, filtered and non-chlorine tasting water from there.
It works well, but it only deals with a few litres at a time.
When we take a jug full from it, we fill that same jug with
tap water and pour it in first, so we always have a good
supply, albeit some time later, since it takes so long to passively filter through.
We also have another benchtop water cooler/heater type
thing. It uses a similar filter system in the top tank, and any
water drawn off is filtered, as it comes from the bottom tank.
The unit has a hot and a cold tap, so we can have chilled
water and heated water (but not boiling).
It’s a relatively cheap appliance, and as a cooler, it is OK.
As a heater, it is passable, but you wouldn’t get a steaming hot coffee using that water. The cooling and heating
are achieved by a Peltier element, a cheap and effective
way of achieving heating and cooling, using the Thermoelectric Effect.
They aren’t that energy-efficient, but devices like this are
passable and much cheaper than the alternatives. A proper
water cooler uses refrigerant in a heat exchanger system
and deploys a decent heating element for hot water. But
this one is not that advanced. We mostly just use it for its
cool(ish) water.
The important thing is that it is filtered; we can always
put ice in it, or fill a jug and put it in the fridge.
Items Covered This Month
• Water woes
• Repairing a Beyonwiz DP-P2 video recorder
• Getting around a water pump
• Fixing a Bose SoundDock Series 1
Dave Thompson runs PC Anytime in Christchurch, NZ.
Website: www.pcanytime.co.nz
Email: dave<at>pcanytime.co.nz
Cartoonist – Louis Decrevel
Website: loueee.com
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July 2025 83
So, it is a useful appliance regardless of the inability to
get water really hot or cold. I hear it occasionally go into
cooling mode, and we can usually trigger it by emptying
the filtered water reservoir and letting unfiltered water drip
through the filter system. As soon as the water in the tubes
below the tanks gets a little warmer, a thermostat triggers
the relevant element to heat or cool.
Peltier problems
With a single Peltier element, simply reversing the polarity of the power supply dictates whether the element heats
or cools. They are used in all kinds of mini fridges and food
warmers, but it gets a little trickier in a water dispenser
with both hot and cold functions.
They could use complicated switching in order to heat
one side and cool the other, or they can just use two Peltier elements, one for hot and one for cold. The latter is
what I found here.
The problem arose when we noticed the water was not
being chilled anymore. When I tried the warm water, that
side was working. I emptied the bottom reservoir and filled
it with room-temperature water, but while the cooling fan
kicked in, after half an hour, the water was the same temperature. This required a closer look.
I emptied all the water, or as much as I could, unplugged
the cooler and removed the vented bottom of the unit. As
usual, there were security screws used throughout. It is not
really a problem when you have the bits, so there’s no real
‘security’. In other words, it’s all a waste of time and money.
The bottom came away cleanly enough and exposed a
printed circuit board (PCB), along with the heating and cooling modules. This, surprisingly to me, was a wholly integrated unit, which consisted of side-by-side piggy-backed
small water tanks, with inlet and outlet tubes.
A Peltier element was mounted on one face of the tanks,
and a CPU-type heatsink and cooling fan was mounted on
each end. I guess the fans draw air from the elements rather
than blow air through the heatsinks. Either way, I’d never
seen anything like this before.
I mean, I’ve played with Peltier elements – I can buy
them at Jaycar, for example, and found them interesting to
experiment with. But I have not seen them used like this.
The difficulty I was facing was that the elements are
glued to the water tanks with something that, by the looks
of it, is military-grade adhesive. Some gentle persuasion
proved it wasn’t going to let go easily. I guess I could have
literally scraped the element off, but that was going to be
too messy. And what could I use to stick it back on with?
Some kind of heat-resistant epoxy?
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Silicon Chip
This was starting to look like it wasn’t worth investing
more time in. I deduced this could be a standard type of
part for these big box cooler/heaters and so hit the Chinese
sites for a similar part.
True to form, there were literally hundreds of all different types and styles for sale there.
I filtered (har!) out the ones that might work, just based
on looks alone, and found a few that handily had measurements listed with them – most don’t. As there were
no part numbers anywhere on this one, that made it a little more difficult.
The old switcheroo
I jumped to the conclusion that the voltage and current
supplied to the elements would be pretty much the same
as all the others, so it was simply a matter of finding an
assembly that was around the same size and fitted inside
the space. It would also be a bonus if the mounting holes
lined up, but I could work around that.
With no specific mounting measurements listed, it was
a gamble, but since the overall sizes and shapes were reasonably consistent between the ones I was looking at, I
felt confident one would fit OK. I doubted whether this
appliance manufacturer – a cheaper brand – would use
something other than what was inexpensive and readily
available.
I took the plunge and ordered a replacement that looked
pretty much identical to mine and waited the usual months
for it to make its way here.
It eventually did arrive. At least the filter side of the
thing still worked, even if it didn’t cool the water. The new
assembly was very close to the old one.
The biggest hassle was taking off the single-use clips
from the soft rubberised water hoses. These must have been
put on with a machine of some type, so I had to carefully
cut them off without damaging the hoses beneath. I didn’t
want to have to replace them, too.
The module had been hard soldered in – I guess they
couldn’t stretch the manufacturing budget to some PCB
connectors. It was simply a matter of mounting the new
one and soldering the wires to it. Two of the holes lined
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up, but the others didn’t. Although I could only use two
of the four, the module was solidly mounted.
The acid test was plugging it in, filling it with water and
firing it up. The fans came on as the switch was toggled,
and all the usual lights came up to show it was heating and
cooling. I left it for 20 minutes, checking occasionally for
the usual burning smells and any indication that things
were not happy.
It seemed OK, and the water was cooling. After a while,
the fans stopped, so I assumed things were up (or down!)
to temperature. I replaced the bottom cover and put the
unit back into its usual position and it has been running
now and cooling the water for months, so I consider it
repaired.
At the end of the day, though, it would have likely been
cheaper and less hassle to just go and replace the whole
unit. But, that means the rest of this one would end up in
a landfill somewhere, so it is a mixed blessing that we can
at least buy a part that will work in it.
Again, it wasn’t essential that this thing cooled the water;
we really just use it for filtering, but it irks me that something would fail after a relatively short time, no matter
how inexpensive it may have been to buy. The Serviceman’s Curse required I at least tried to repair it and get it
back in working order!
Beyonwiz DP-P2 PSU repair
I found a listing on eBay for a brand new Beyonwiz DP-P2
personal video recorder (PVR) for $20 plus $20 postage. I
thought that was odd, as this model is now more than 10
years old. Also, a working DP-P2 is worth more than $100;
even one in non-working condition is worth more than $20.
I wondered if it was a scam, so I sent my mate the link
with the subject “Too good to be true”. Imagine my surprise when he emailed me back and said he’d bought it!
He said because it was so cheap, he took the chance on
it and even if it was a scam, he could get his money back
with PayPal anyway.
A few days later, he emailed me to say that the unit
arrived, but it was not brand new and it had no remote or
anything else with it, just the PVR. When he connected it
and turned it on, it came up with ERROR 0000. I told him
to take the lid off and look at the power supply board to
see if there were any bad capacitors. He emailed me back
that they all looked fine.
A high percentage of failures in these units are caused
by bad capacitors; I’ve fixed many.
He suggested sending the unit up for me to have a look
at, but I said the postage cost is too high; I said to just take
the PSU out, send that and I will have a look at it. I would
see if I could fix it, but there were no guarantees.
A few days later, the power supply board arrived. I could
see that six large electrolytic capacitors had been replaced,
three of which were a larger physical size than the originals. The soldering was good and there were no dry joints
on the board, so it would be a tricky one to fix.
When I had some time, I got out one of my working DP-P2
PVRs and fitted my mate’s PSU into it. Sure enough, it came
up with ERROR 0000, so the PSU was definitely faulty.
I got the board back out and started checking it over. I
first tested all the diodes with my in-circuit transistor and
diode tester, and they all tested good. On one of my other
PSU boards, I’d found that D12 and D13 (UF5402 200V
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July 2025 85
ultrafast diodes) were faulty, but on this PSU board, they
were still good.
The next things to check were all the electrolytic capacitors. I grabbed my ESR meter and started testing them. I’d
recently repaired a DP-S1 PSU that had six faulty small
capacitors. Checking over this DP-P2 PSU board, I found
that most of the capacitors were good, but C7 and C11 (both
50V 33µF types) read very high at around 5W when they
should be less than 1W.
I checked my salvaged capacitors, but I did not have any
of this value. Then I remembered that I may have purchased
this value some time ago and, on checking my new parts, I
found them. I replaced the two capacitors and put the PSU
board back in the PVR and switched it on.
This time, it came up showing Channel 7 Melbourne
on the front display. I connected the HDMI cable to my
HDMI switch and turned on the TV. I checked the hard
drive, and there were several recordings, so I skimmed
through a couple of garden shows and everything worked
fine. Then I connected up the aerial and tuned in the
local channels.
So, my mate’s PSU was now working and I could send
it back to him. While I had this PVR out, I had a look at
the three DP-P2 PSUs that I had not yet fixed. I’d noted
on them which voltages were missing and I’d taken the
12V regulator out of one of them in the course of troubleshooting it.
This just happened to be the PSU that I’d replaced D12
and D13 on. I looked at the other two non-working boards
as to which voltages were missing and I determined that
the 12V regulator on one of the boards should be good, so
I removed it and fitted it to the PSU that I’d replaced D12
and D13 on.
I fitted the PSU to the PVR and turned it on. It now
worked, indicating that my previous troubleshooting
(which I hadn’t got back to) had found the last faulty
component on this PSU. Looking at the other two units,
I ordered some parts on eBay that I suspected of being
faulty on these boards. I will get back to them when the
parts arrive.
Time came to post the PSU back. He received it a few
days later and fitted it to the Beyonwiz DP-P2 PVR, and he
reported that it is now working correctly. This was another
win for both of us.
Bruce Pierson, Dundathu, Qld.
Water pump workaround
About a year ago, we had a lightning strike in our backyard at about 1am. The EMP tripped the main circuit
breaker. We discovered the extent of damage the next day,
which included a damaged workshop air conditioner, the
NBN box, oven, printer and the water tank pump. Lightning
had actually struck a tap that was connected to the pump.
It was covered by insurance, but we never got around to
fixing the water pump. The tank is on the high side of the
block, so gravity feed is adequate for the low side. It has
been on the back-burner for a year, but I finally got around
to looking at it.
As it turns out, the motor survived, but the control electronics were completely blown apart. As with most devices
these days, getting a spare was impossible; you can only
buy the whole assembly. The photo of the control board
shows how much damage several thousand volts will do.
Some years ago, I bought a couple of remote control modules. These run from a 12V plugpack and the relay switches
up to 10A, more than enough for the motor. I forgot why I
bought them and they were never used.
I put the module inside a plastic box attached to the
wall next to the water tank; it is under cover so there was
no need for waterproofing. The remote range is not great,
about 20m, but that’s adequate. So now I can switch the
pump on manually if it’s needed.
I then added a mains timer for the plugpack to limit the
time the pump is on. Instead of spending about $300 on a
new pump assembly, the repair cost was effectively zero,
as I already had all the bits.
Charles Kosina, Mooroolbark, Vic.
Bose SoundDock rejuvenation
My daughter was cleaning out her garage and found an old
Bose SoundDock Series 1. She suggested
that it would be nice to get going again
as the sound from it was very good. So I
ended up with another job. The SoundDock looked in good condition, but there
was no power supply or remote control.
The SoundDock was designed to have
an original iPod with a 30-pin connector
plugged into it as the music source, but
that was long gone. I found a Bluetooth
receiver on the internet that was designed
to replace the iPod, so I ordered it.
I remembered repairing the power supply some years ago; it was a ±18V unit. I
figured I could find two suitable power
packs in my box of spares and get it going.
I found the correct pin information on
the net and connected the power packs.
I plugged the Bluetooth module in and
applied power. The LED on the module
The power supply from the Beyonwiz
DP-P2 personal video recorder.
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Australia's electronics magazine
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The photo at upper left shows the water pump assembly,
while the photo above is of the very obviously damaged
control board. The adjacent photo shows one of the remote
control modules that I had lying around. The relay in these
modules are rated up to 10A, making them perfect for this
motor.
did not even light up, so it was not getting power. I decided
to test the Bluetooth module separately, so I found an old
iPod charging cable and connected the Bluetooth module to
it. The LED lit up, and I was able to connect my phone to it.
So it looked like there was no power getting to it when
it was plugged into the SoundDock.
I removed the covers from the SoundDock and found
some components that had obviously overheated. With no
circuit diagrams, it would be a nightmare to repair.
I had a 30W + 30W stereo amplifier board left over from
another project, and it looked like I could fit it in place of
the original amplifier. I connected the new amplifier to the
speakers and wired the output of the Bluetooth module
to it. Once connected to my phone, the audio output was
quite acceptable, so it was just a matter of fitting the new
amplifier in the existing case.
I made a sheet metal plate to fit and screwed the new stereo amplifier in place. I wanted to keep the original input
board with the 30-pin connector, so I found some information about it on the internet and wired the audio out to
the new amplifier. I decided to use a 12V 2A power pack,
so I had to add a 7805 regulator to drop the 12V to 5V for
the Bluetooth module.
I put it all together and discovered that the Bluetooth
module produced an audio announcement saying it was
powered up and connected, but the audio level was way
too high, so I attenuated both channels using a resistor
divider network to give only 25% of the original signal
level. The actual music level could be controlled by the
audio player on the phone.
Finally, I designed and 3D-printed a plate to fit around
the Bluetooth module socket and fitted a power connector
to the back so the plugpack could be easily disconnected.
Now we had a great sounding music system for my
daughter’s study.
SC
John Western, Hillarys, WA.
The internals of the Bose SoundDock is shown above with
a close-up shown at right.
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July 2025 87
Vintage Radio
The Eddystone EC10 Mk2
All Transistor Shortwave Radio
This all band set was UK-based Eddystone’s first release of an alltransistor receiver in 1973. It’s a good performer if noisy at full gain. It
has a switchable AGC, a BFO, a bandpass filter and a fine-tuning knob.
Its biggest weakness is non-linear tuning.
By Ian Batty
Y
ou may recall that Sony began
with a rice cooker and National/
Matsushita with a bicycle lamp. However, Stratton and Company (who
would become Eddystone) began
in 1860 making much more modest
goods: steel pins and hairpins.
Stratton expanded into gentlemen’s
jewellery, ladies’ compacts, a variety
of small metal products – including
knitting needles, thimbles, hat pins
and crochet hooks – and a whole range
of do-it-yourself kits for making model
ships and aeroplanes, pearl flowers,
seagrass stools and timber bead mats.
Changes in fashion saw the demand
for hairpins slump in the early 1920s.
Needing new products to survive, manager George Laughton’s son (a radio
enthusiast) asked a simple question:
“Why not make wireless components?”
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Silicon Chip
It was 1923 and the die was cast.
Needing a trade name, what could be
better to project an aura of reliability and prominence than that of the
world’s first open ocean lighthouse,
the Eddystone Light? First operational
in 1699, it had given over 200 years of
faithful, life-saving service by 1923.
Listeners in 1927 must have been
fascinated by Eddystone’s first shortwave receiver. They could see the parts
moving and the valves light up through
a glass panel.
Eddystone expanded, becoming a
world-famous leader in communications equipment. You’ll find their
products, especially receivers, in collections around the world. I reckon
that any collection lacking an Eddystone is ‘yet to be completed’.
The year 1973 was Eddystone’s
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50th anniversary, and valve-equipped
receivers were being phased out. It
was not due to a lack of demand but
because obtaining many of the components was no longer possible.
The EC10, Eddystone’s first all-
transistor receiver, looks the goods.
It has a large, easy-to-read dial, the
famous flywheel-equipped tuning
mechanism and a compact size. But
don’t be fooled by that size – it competes well with its valve-equipped predecessors, but with the convenience of
hundreds of hours of operation using
internal batteries.
Description
The EC10 is a general-coverage,
single-conversion superhet that operates from batteries or a plug-in mains
supply that replaces the battery
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The rear of the EC10 has the antenna socket on the left (three
to allow for a wire antenna or telescopic rod) and both high and low impedance audio outputs on the right.
compartment. It uses ten transistors:
five alloy-diffused high-frequency
types in the tuner/IF section and five
alloyed-junction types in the audio
section, all PNP.
Its coverage is 550kHz to 30MHz and
intermediate frequency (IF) is 465kHz:
• Band 1 is 18MHz to 30MHz.
• Band 2 is 8.5MHz to 18MHz.
• Band 3 is 3.5MHz to 8.5MHz
• Band 4 is 1.5MHz to 3.5MHz.
• Band 5 is 550kHz to 1.5MHz.
The Mark I uses three diodes, while
the Mark II adds three, for a total of
six. It features a signal strength meter,
which is helpful when tuning. The
Fine Tuning control, which operates
a variable-capacitance diode (varicap)
in the local oscillator (LO) section, is
essential when tuning signals in the
highest band.
All models feature an RF gain control and a beat frequency oscillator
(BFO) for use with CW or SSB signals.
There is also a switchable audio filter
centred on 1kHz to improve the clarity of CW signals. The audio output
is quoted as 800mW into the internal
speaker. An external speaker can be
used, and there is a high-impedance
audio output for connection to an
external audio amplifier.
The set can operate with various
antennas: unbalanced, balanced or a
short telescopic rod. Its input impedance is 75W on Bands 1 through 4 and
400W on Band 5. Sensitivity is quoted
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as better than 5μV on Bands 2-5 and
better than 15μV on Band 1.
The EC10’s only limitation is the
failure to use a straight-line frequency
tuning capacitor, so the frequency divisions are compressed towards the top
end of each band.
Construction
The set is well-built, with the traditional ‘flywheel’ on the tuning knob.
This allows the highly-geared tuning
system to spin rapidly from end to end
across the selected band.
The chassis and front panel withdraw easily from the case and the
internal construction is sound. Most
electronic components are mounted
on two printed circuit boards: one for
the tuner (RF) and the other for IF/
audio. The IF/audio board is mounted
copper-side on top, so measurements
are easily made.
Unfortunately, two of the IF transformers use double slugs, and the service notes describe the relocation of
the IF/audio board to allow access to
the inside slugs for a complete alignment and other work.
Circuit description
I could not find a completely legible circuit diagram online, so I have
redrawn Eddystone’s original for clarity and ease of description, including the power supply circuit from
my EC10 MKII. I have moved some
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components from their original locations but retained Eddystone’s numbering – see Fig.1 overleaf.
I have added DC circuit voltages to
the diagram, with signal voltages in
two tables at the right of the drawing.
Note that the band change switch
sections (S1a to S1j) are all shown
with Band 2 selected and viewed
from the rear. Band 1 is, thus, fully
anti-clockwise, while Band 5 is fully
clockwise.
Eddystone showed each section
from its contact side. I found this confusing, as some sections have their
contact sets on towards the front of
the set and others to the rear. This
demanded that one visualise some
sections rotating clockwise and others anti-clockwise.
The EC10 uses a grounded-base RF
amplifier. We’re probably familiar with
common-base’s low input impedance,
typically in the low tens of ohms, and
its current gain of just under unity.
For these reasons, voltage amplifier
designs adopted the common-emitter
configuration, with its much higher
input impedance and current gain.
However, the common-base configuration has a very high output impedance, in the hundreds of kilohms at
audio frequencies. As noted in the
article on General Electric’s P-807
5-
t ransistor set (November 2015
issue; siliconchip.au/Article/9405),
common-base’s power gain – due to its
July 2025 89
high output impedance – can approach
that of common-emitter.
Common-base’s low feedback capacitance also makes it more suited to
operation at higher frequencies than
common emitter, even in wideband
amplifiers such as video output stages
in CRT-based televisions. Common-
base’s low input impedance is easily
matched in RF circuits by tapping the
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driving tuned circuit or matching coil.
Common-base’s high output impedance minimises loading of the EC10’s
selected RF transformer (L7~L11) primary, thus realising the maximum Q
for each primary tuned circuit.
Local oscillator TR3 also operates
in grounded-base configuration. While
the OC171 can, in theory, work easily to the top end of the HF band in
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common-emitter, using common-base
ensures more constant output as the
set is tuned to 30MHz.
Tuner section
All trimmers are 6-25pF types, while
all transistors in the tuner and IF sections are alloy-diffused OC171s in
four-lead metal TO7 cases.
Antenna selector S1a selects
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Fig.1: my redrawn EC10
Mk2 circuit diagram.
transformers L2 (Band 1) to L6 (Band
5). Bandstop filter L1/C2 is added in
series on Band 5 to improve IF rejection. The input can be unbalanced
(A1 to ground, input to A2), balanced
(to A1 and A2), or a factory-supplied
telescopic rod to A3.
The RF stage is protected against
damaging overload by D4/D5, back-toback silicon diodes that limit the signal
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at the selected antenna coil primary to
about 600mV peak-to-peak.
The antenna transformer secondaries are tuned by the tuning gang’s
antenna section, C15. Bands 5 and 4
use the full capacitance sweep of C15,
while Bands 3, 2, and 1 are restricted
by band spread capacitors (C8/C9/
C10). Band 1’s range (around 1:1.7) is
further limited by 390pF padder C11.
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All transformers in the front end are
slug-tuned for low-end alignment and
trimmer-tuned for high-end alignment.
S1b connects the selected antenna
transformer secondary to the tuning
gang’s antenna section, C15. A selector
ring on S1b shorts the unused antenna
transformers’ secondaries, eliminating
the possibility of absorption and dead
spots in tuning.
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Shock hazards
I have found English-manufactured equipment to generally have dangerous mains wiring. The EC10 has a plug-in power supply, with four-pole plug PL1 connecting the supply
to the main chassis. Two wires carry the 9V DC supply, and the other two carry mains
to the on/off switch in the RF gain control.
The wiring is lightweight gauge, and its connections to the plug are not insulated. I
can vouch for this, having found out by almost throwing the set off the bench in reaction to a nasty mains shock! Similarly, the connections to the back of the switch in the
RF Gain control are not insulated.
Two yellow paper dots should remind the user how to connect the plug if they have
not fallen off. Although the plug is mechanically polarised, it may be possible to insert
it backwards, reversing the -9V DC polarity and potentially destroying the set. Additionally, the power supply’s mains lead simply passed through a grommet with no cord
anchor/clamp.
I rectified the first hazard by disconnecting the leads to PL1, sliding heatshrink tubing
over each lead, then reconnecting and shrinking the tubing to prevent any possibility of
contact with the live terminals. I also fitted a cord anchor to securely retain the power
supply’s mains lead. I strongly recommend that you examine any equipment – of any
origin, but especially English – for safety and proper insulation of mains connections.
Left: two of the tabs on
PL1 carry mains and are
not insulated from the
factory.
Below: the rest of the
power supply section.
The selected transformer secondary
connects, via S1c, to the emitter of RF
amplifier transistor TR1. This has AGC
applied to its base, which is bypassed
to RF ground.
TR1’s collector connects to the primary of the selected RF transformer
(L7~L11) via S1d. As with S1c, this
includes a shorting ring. L7/L8 are also
band spread via C20/C26. The selected
transformer connects to the RF section
of the tuning gang (C27) via S1e. Like
Band 1 antenna transformer L2, Band
1’s RF transformer, L7, has a 390pF
padding capacitor, C19.
The selected RF transformer’s secondary is connected to the base of converter transistor TR2 via S1f. The local
oscillator signal is supplied to TR2’s
emitter from the selected LO transformer (L12~L16) via S1h. Capacitor
C19 reduces the LO signal’s injection
level on Band 1.
The LO must track at 465kHz
above the incoming signal, so it uses
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a combination of the usual padding
and band spreading. Bands 5, 4 and
3 use the usual padding capacitors in
series with the gang.
Band 5’s padder capacitor C38
(500pF) seems about right for the
broadcast band, but capacitor C37
for Band 4 is a non-standard value
of 1.4nF. Band 3 uses another non-
standard value of 7nf (C46).
The increasing values of these padder capacitors means that they force
progressively less padding effect as the
LO’s frequency span rises from Band 5
(most effect) to Band 3 (least).
For Band 2 (8.5~18MHz), a 465kHz
offset between the LO and signal frequencies is negligible, so C45 (47nF)
is not for padding. It’s simply there to
block the LO’s DC collector voltage,
which would otherwise be shorted to
ground via the unselected LO primary/
tuned coils in the L12 to L16 coil set.
Band 1 is spread by 400pF capacitor
C44 to hold the LO to a restricted span
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(around 1:1.7), so it tracks with Band
1’s antenna and RF transformers. The
LO frequency span is restricted by C44
(400pF), but without the IF offset we’re
accustomed to in broadcast superhets.
The MKII’s fine tuning is provided
via varicap diode D6. This is most
effective on the higher bands. The
tuner section is fed from a stabilised
-4.5V supply, derived from the main
supply via zener diode D3 on the IF/
AF board. This reduces tuning drift
due to mains variations or battery ageing. Drift figures are quoted at better
than one part in 104 (<0.01%) per °C.
Converter transistor TR2 feeds the
IF signal via a shielded cable to the
primary of first IF transformer IFT1
on the IF-AF board.
IF section
Both IF amplifier transistors (TR4/
TR5) are OC171s. These alloy-diffused
types exhibit low feedback capacitances of around 2pF, so they operate without neutralisation. TR4 has
AGC applied, while TR5 works with
fixed bias.
TR4’s supply is decoupled by 1.5kW
resistor R24. The voltage drop across
this resistor reverse-biases AGC extension diode D1. Its anode, connected to a
tap on first IF transformer IFT1, is held
close to the supply voltage via the converter’s 100W decoupling resistor R18.
As the AGC begins to control TR4,
its collector current falls, reducing
the voltage drop across R24. Strong
signals will bring D1 into conduction and dampen the signal at IFT1’s
primary. This means the EC10 has
three gain-controlled elements: the
converter, the first IF amplifier and
the extension diode, giving a near-
constant output over a wide range of
signal levels.
IF transformers IFT1 and IFT2 both
have tuned, tapped primaries and secondaries. Final transformer IFT3 uses a
tuned, tapped primary, but an untuned
secondary to feed the low impedance
of demodulator diode D2.
The demodulator feeds audio to the
low-level audio output and, via the
volume control, to the audio section.
The DC voltage across the volume control also drives the 100µA Carrier Level
meter via multiplier resistor R48a.
The demodulator’s output supplies
the AGC line via R28, with the audio
signal filtered out by C63.
AGC is useful when receiving
amplitude-
modulated signals but is
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not effective when receiving CW/
MCW (‘Morse’) or single-sideband
(SSB) signals. So the AGC can be deactivated by S2. This switch cuts off the
AGC voltage and biases the AGC line
to a fixed value via R22, while also
reducing the sensitivity of the Carrier
Level meter via R49a.
The AGC line is also affected by RF
Gain control RV1. This is in series with
the bias divider for TR4 (R20/R21),
allowing the lower part of the divider
to increase in resistance. This means
that the ‘top’ end of R21, which connects directly to the AGC line, will
become more negative as the gain control takes effect. The maximum gain
reduction is about 30dB. RV1’s effect
is augmented by the action of AGC
extension diode D1.
With no carrier, SSB signals cannot
be resolved unless one is reinserted at
demodulation. TR6, the beat frequency
oscillator (BFO), generates a 465kHz
signal that is fed back, via 1pF capacitor C67, to the collector of first IF transistor TR4.
The BFO frequency is variable, via
BFO Tune capacitor C70, to allow
the exact adjustment needed to produce speech from an SSB transmission, rather than ‘duck talk’. Adjusting the BFO to produce a 1kHz tone is
helpful when receiving weak CW signals and takes advantage of the 1kHz
audio filter’s narrow passband when
activated.
The set can be muted using the
Standby switch, which removes bias
from the RF amp and the first IF amp
by shorting the AGC line to ground.
It’s a two-pole switch, with its second
section available for custom wiring to
control external equipment.
allowing headphone-only operation.
The output stage works with fixed bias,
lacking the temperature compensation
that was common in domestic receivers of the day.
Power supply
Power is supplied either from a
plug-in battery pack containing six D
cells, which were available virtually
Audio section
everywhere at the time, via 12V or
In regular operation, the first audio 24V adaptors, or (for my set) a plug-in
stage transistor TR7 (an OC81) acts as 110/240V mains supply.
a simple preamplifier with load resisThe set connects to the power suptor R40. When the Audio Filter is acti- ply via a four-core cable carrying the
vated, audio bandpass filter L18/C76 supply voltage and connections to the
is put in series with R40. The filter, Operations switch S6, part of the RF
tuned to 1kHz, gives a very narrow gain control, which selects between
audio passband, greatly increasing a mains or battery power.
1kHz tone above the background noise.
Be aware that the plug on the set side
As noted earlier, setting the BFO is not insulated, leaving two exposed
for a 1kHz tone allows the resolution metal connections at mains potential.
of weak CW signals in the presence See the panel on shock hazards!
of atmospheric noise or other interThe mains power supply uses a
ference.
transformer, selenium bridge rectifier
TR7’s output goes to audio driver and pi filtering. The output voltage is
transistor TR8. This feeds phase- held to -9V by shunt rectifier diode
splitter transformer T1, which in turn D101. I found that this failed to regufeeds the two output transistors, TR9 late with low mains voltages, around
and TR10, both OC83s. They form the 220V, as shown by the dial lights flickpush-pull Class-B output stage, deliv- ering on strong audio output.
ering audio to the speaker via output
The internal dial lights are switched
transformer T2.
by the momentary Dial Lights pushbutThe EC10 has a Phones socket that ton S5, allowing power conservation
disconnects the internal speaker, during battery operation.
The top view of the Eddystone EC10 radio with its cover removed. The resistor and
capacitor added on this side of the board wire likely added at the factory as running changes.
History and repairs
I bought my EC10 at auction in Hawthorn back in the 1990s and it sat on
the shelf for some years. In the early
2000s, I moved to Harcourt, near Castlemaine and finally popped it onto
the test bench. On examination, it
was pretty well dead in the RF section, although there was noise from
the speaker.
Examination showed that the
antenna coil switch had suffered a
broken wafer. I desoldered all the connections, applied superglue to each
side, replaced it and rewired it. I was
able to get signals, but the sensitivity was still very poor. I aligned and
calibrated the RF stages, but the gain
was still low.
Loosening jammed slugs
The IF showed a ‘double hump’,
indicating severe misalignment. On
correctly aligning the IF, the gain came
up to the specified sensitivity of better
than 5μV on Bands 5 to 2 and better
than 15μV on Band 1.
There are two sizes of coil slugs in
the EC10: those in the RF section with
hexagonal centre holes, and those in
the IF transformers with continuous/
“through-hole” screwdriver slots. Be
aware that these need a special long
flat-bladed tool. Both types were either
loose or jammed. I carefully freed all
the jammed ones, but I wondered what
to do so I could adjust them to position
and not have them move.
I long ago gave up on wax, liquid
paper and nail polish, as I hope we all
1. Does the slug need alignment? You can save effort and time by using a ‘magic wand’,
a piece of heatshrink tubing maybe 10cm long with a slim ferrite slug in one end and a
brass slug in the other to find out before going any further.
Slide the ferrite end into the coil can. If the signal improves, the coil needs more inductance for correct alignment. If that makes things worse, try sliding the brass end into
the coil can. If the signal improves, the coil needs less inductance to align correctly. If
both slugs make things worse, the coil is correctly aligned.
2. Do not use spray lubricants. Most of these include organic oils that can actually jam
a slug in its thread.
3. If the slug has a screwdriver slot and the slot is damaged, trying to screw the slug out
of the coil towards you is the worst of all worlds. You are trying to drive the slug back
against the force of the screwdriver, and there may be slug debris in the threads! If the
coil has two slugs, try screwing the opposite slug right out of the coil.
Now that you have a (hopefully) untouched slot available on the inside of the jammed
slug, use that good slot to carefully screw the jammed slug into the centre and out the
end you are driving from. You can improve your chances by cleaning the coil former’s
available screw threads as thoroughly as you can before trying this. Some threads in
coil formers conform to Whitworth/SAE standards.
4. If you cannot get to the good end of the slug, try the ‘fridge move’. Put the set in the
fridge and leave it for a few hours. Differential contraction between the slug and the
former may loosen it once it all warms up.
I have also successfully used a variable-temperature hot air gun to cause differential expansion. Set it to around 70ºC. Warm the coil, occasionally withdrawing the gun
to feel how hot the coil or its can is. If you can leave a finger on the can for a second or
two, that’s good. Anything hotter risks melting or distorting plastic parts.
This method will likely soften any wax, grease or vanish, easing the job. I used this
method to recover an Emerson hybrid’s IF trannie that I had unwisely used WD-40 on.
5. If the slug has a hexagonal hole (TV IF strips, Eddystone EC10 type) or a slim slot
(‘Neosid’ type) going all the way through, it may be cracked into two or more parts along
its length. This is the worst of all possibilities, and you may need to replace the entire coil.
Destroying the slug and shaking the bits out may be possible, but you can do a lot of
damage to the coil l former. In the worst case, where you cannot get an exact replacement for the windings, you may be able to find a similar, good coil l former and can, warm
the coils, draw them off from the jammed former, and replace them onto the good spare.
6. If you get the slug out, thoroughly clean out the former’s threads with a tiny bottle
brush or compressed air (gently!). Do not use solvents, especially acetone, as they will
dissolve many plastics. Test with a good slug or a suitable thread tap. Once the thread
is clear, you’ll find that slugs/taps are often a little loose in a clean former.
7. When you replace the slug(s), use thin ‘plumber’s tape’ to stop the slugs from moving – it will hold them in place but will not gum up or jam.
have. My ‘magic ingredient’ is Teflon
plumber’s tape, which I also use in my
plumbing and irrigation work. With
the RF coils’ large threads, I found I
needed to fold a length of tape over
itself a few times to make the slugs fit
snugly. I used a single wrap of tape for
the finer-thread IF coils.
I used the set for a while, and two
subsequent faults appeared. First, the
BFO (needed for CW & SSB reception)
stopped working. The oscillator used
an OC171. This transistor had presumably succumbed to the dreaded
‘whiskers’, where minute dendrites
grow between the transistor element
and the grounded metal case within
the device and eventually stop it from
working.
Since the BFO operated at around
465kHz, the OC171 was considerably
under-rated. I had no spares, but an
OC400 (with a lower cutoff frequency)
worked just fine. I did need to adjust
the circuit capacitance to bring the
BFO back to the correct frequency, but
it calibrated up correctly.
The second fault appeared with
massive amounts of breakthrough of
the local FM band stations into the
broadcast band. I lived less than 10km
from Mount Alexander, which hosts
most of the FM radio and TV transmitters for the Central Highlands and
Goldfields.
On examination, a wire connecting to the broadcast (Band 5) antenna
coil had come adrift, open-circuiting
the tuning for this stage. Given the
amount of signal flooding in on the
FM band, it appears that the front
end was rectifying the FM signals
and allowing them to cross-modulate
into the IF.
The audio filter worked, but was
centred on about 800Hz and would
not adjust sufficiently. I replaced the
100nF tuning capacitor C76 with a
56nF type, and got the filter to its 1kHz
design frequency.
A curious thing
The alignment guide states that
injecting a signal at the input to the
IF strip needs only about 4μV to give
50mW audio output if the alignment
is correct. That implies the entire RF
section has near-unity gain. This mirrors the advice for an Eddystone VHF/
UHF set, the 770U, which I’d previously worked on.
It appears that Eddystone regards
the RF section as a ‘preselector’,
siliconchip.com.au
An underside view of the set. The EC10 uses 10 transistors and 18 inductors which you can see tightly packed into the
central section of the board. Note the speaker, which has a relatively rare rated impedance of 3W.
siliconchip.com.au
Australia's electronics magazine
July 2025 95
relying on the IF/AF sections to provide the majority of the gain.
Performance
For a first outing, it’s pretty good. I
was surprised that Eddystone did not
use a gang with straight-line frequency
plates. The result is that frequency
calibration is compressed towards the
top end of each band, as happened
with pocket transistor radios of the
day. Roger Lapthorne (G3XBM) noted
that the entire 10m band (28MHz to
29.7MHz) is only about 10mm wide
on the scale.
Pye Australia’s contemporary PHA
520, developed for the Colombo Plan,
did use a straight-line frequency cut,
making tuning much easier, especially
towards the top end of its 14.5~30MHz
band. The Fine Tuning control’s
authority varies, giving a range of some
±30kHz at 29MHz, but only around
±2.5kHz at 1400kHz.
The EC10 specification requires
50mW output, with a signal-plus-noise
to noise (S+N:N) ratio of 15dB from a
signal under 6µV on all bands. Table 1
shows my actual measurements.
Superhet receivers are prone to
image response interference, where a
signal that is twice the IF frequency
above (or below) the desired signal
will also be received. This is rarely a
problem with broadcast radios, where
the antenna tuned circuit can attenuate
the image by 60dB or more. A tuned RF
amplifier – by virtue of its tuned interstage circuit – will improve this figure.
At higher frequencies, image rejection is compromised as the bandwidth
of front-end tuned circuits widens.
The EC10 displayed such behaviour
– see Table 2.
At 600kHz, the -3dB bandwidth is
±2.2kHz, while at -60dB, it’s ±12.7kHz.
The audio bandwidth from the volume control to the speaker is 80Hz to
11kHz (-3dB). While that is impressive, the response from the antenna to
the speaker is only 60~1750Hz due to
the IF strip’s narrow bandwidth.
The audio filter, useful with CW/
MCW reception, has a -3dB bandwidth
of around ±50Hz at 1kHz. Audio output was around 400mW at clipping,
with 10% total harmonic distortion
(THD). At 50mW, THD was a low
1.8%, rising to 3% at 10mW, evidence
of crossover distortion at low levels.
Figs.2 & 3: the signal strength meter indication vs input signal level with
AGC on (left) and off (right).
Frequency Input signal level
Using three control stages, the AGC
gave a 12dB rise for a signal range of
90dB. Wow.
In use
For the first-generation unit that it
is, the EC10 works well. It is noisy at
full gain, with S+N:N ratios as low as
3dB. This implies that the equivalent
front-end noise is equal to the actual
signal level.
As noted with the Sony TR-712,
it’s possible to get a lot of gain with a
good amplifier design. Still, such an
approach is compromised by device
noise, for which germanium transistors are especially bad.
Additionally, the background noise
across the broadcast/HF bands, even
in areas well away from the ‘fog’ created by switchmode power supplies, is
commonly “some tens” of microvolts
per metre. Such a noise floor means
that the EC10’s useful performance
will, in practice, rival that of valveequipped competitors of the day.
At my location, on Victoria’s Mornington Peninsula, the broadcast band’s
residual noise level well exceeds
50μV/m!
This set, a Mark II, has a signal
strength meter, which measures the
demodulator’s DC output. With the
AGC on, it effectively measures the
AGC voltage, giving an essentially
logarithmic response. Due to the
AGC action, it provides a compressed
indication on signals of any strength,
showing a very broad tuning peak.
With the AGC off, the meter’s indication loosely tracks the input signal’s
strength, reaching the ‘8’ mark at about
35μV. Above that, the set overloads
and the signal becomes distorted, so
either the RF gain must be reduced or
the AGC switched in. For SSB reception, you would commonly have the
AGC off and use the RF gain control
to adjust the set’s gain.
Fig.2 shows that the signal strength
meter response is logarithmic with
AGC on, while Fig.3 demonstrates it’s
linear, with AGC off, up to the point
SC
of overload.
S+N:N
15dB input signal level
600kHz 2.0μV
6dB
6μV
1400kHz 0.3μV ♦
3dB
2.5μV
1.6MHz 1.2μV
3dB
4.5μV
3.5MHz 1.5μV ♦
3dB
5μV
3.8MHz 1.0μV
3dB
4μV
Frequency
Image rejection
8.0MHz 1.0μV
3dB
5μV
600kHz
64dB
9.0MHz 1.2μV
5dB
3.5μV
1.6MHz
53dB
17.5MHz 1.0μV
7dB
3μV
3.8MHz
58dB
18.5MHz 2.0μV
7dB
4μV
9.0MHz
36dB
29MHz 1.0μV
3dB
5μV
18.5MHz
16dB
Table 1 – sensitivity vs frequency ♦ gain was reduced to get a useful reading
Table 2 – freq vs image rejection
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- two 1nF ±1% capacitors (ESR Meter, Aug23; SC4273)
$2.50
- 5V 3-pin boost regulator module (2m CW/FM Test Generator, Oct23; SC6780) $3.00
- 5V 3-pin buck regulator module (2m CW/FM Test Generator, Oct23; SC6781) $4.00
- 0.96in 128x64 white OLED without PCB (SmartProbe, Jul25; SC7397)
$7.50
*Prices valid for month of magazine issue only. All prices in Australian dollars and include GST where applicable. # Overseas? Place an order on our website for a quote.
PRINTED CIRCUIT BOARDS & CASE PIECES
PRINTED CIRCUIT BOARD TO SUIT PROJECT
TINY LED ICICLE (WHITE)
DIGITAL BOOST REGULATOR
ACTIVE MONITOR SPEAKERS POWER SUPPLY
PICO W BACKPACK
Q METER MAIN PCB
↳ FRONT PANEL (BLACK)
NOUGHTS & CROSSES COMPUTER GAME BOARD
↳ COMPUTE BOARD
ACTIVE MAINS SOFT STARTER
ADVANCED SMD TEST TWEEZERS SET
DIGITAL VOLUME CONTROL POT (SMD VERSION)
↳ THROUGH-HOLE VERSION
MODEL RAILWAY TURNTABLE CONTROL PCB
↳ CONTACT PCB (GOLD-PLATED)
WIDEBAND FUEL MIXTURE DISPLAY (BLUE)
TEST BENCH SWISS ARMY KNIFE (BLUE)
SILICON CHIRP CRICKET
GPS DISCIPLINED OSCILLATOR
SONGBIRD (RED, GREEN, PURPLE or YELLOW)
DUAL RF AMPLIFIER (GREEN or BLUE)
LOUDSPEAKER TESTING JIG
BASIC RF SIGNAL GENERATOR (AD9834)
↳ FRONT PANEL
V6295 VIBRATOR REPLACEMENT PCB SET
DYNAMIC RFID / NFC TAG (SMALL, PURPLE)
↳ NFC TAG (LARGE, BLACK)
RECIPROCAL FREQUENCY COUNTER MAIN PCB
↳ FRONT PANEL (BLACK)
PI PICO-BASED THERMAL CAMERA
MODEL RAILWAY UNCOUPLER
MOSFET VIBRATOR REPLACEMENT
ARDUINO ESR METER (STANDALONE VERSION)
↳ COMBINED VERSION WITH LC METER
WATERING SYSTEM CONTROLLER
CALIBRATED MEASUREMENT MICROPHONE (SMD)
↳ THROUGH-HOLE VERSION
SALAD BOWL SPEAKER CROSSOVER
PIC PROGRAMMING ADAPTOR
REVISED 30V 2A BENCH SUPPLY MAIN PCB
↳ FRONT PANEL CONTROL PCB
↳ VOLTAGE INVERTER / DOUBLER
2M VHF CW/FM TEST GENERATOR
TQFP-32 PROGRAMMING ADAPTOR
↳ TQFP-44
↳ TQFP-48
↳ TQFP-64
K-TYPE THERMOMETER / THERMOSTAT (SET; RED)
MODEM / ROUTER WATCHDOG (BLUE)
DISCRETE MICROAMP LED FLASHER
MAGNETIC LEVITATION DEMONSTRATION
MULTI-CHANNEL VOLUME CONTROL: VOLUME PCB
↳ CONTROL PCB
↳ OLED PCB
SECURE REMOTE SWITCH RECEIVER
↳ TRANSMITTER (MODULE VERSION)
↳ TRANSMITTER (DISCRETE VERSION
COIN CELL EMULATOR (BLACK)
IDEAL BRIDGE RECTIFIER, 28mm SQUARE SPADE
↳ 21mm SQUARE PIN
↳ 5mm PITCH SIL
↳ MINI SOT-23
↳ STANDALONE D2PAK SMD
↳ STANDALONE TO-220 (70μm COPPER)
RASPBERRY PI CLOCK RADIO MAIN PCB
↳ DISPLAY PCB
KEYBOARD ADAPTOR (VGA PICOMITE)
↳ PS2X2PICO VERSION
MICROPHONE PREAMPLIFIER
↳ EMBEDDED VERSION
RAILWAY POINTS CONTROLLER TRANSMITTER
↳ RECEIVER
LASER COMMUNICATOR TRANSMITTER
↳ RECEIVER
DATE
NOV22
DEC22
DEC22
JAN23
JAN23
JAN23
JAN23
JAN23
FEB23
FEB23
MAR23
MAR23
MAR23
MAR23
APR23
APR23
APR23
MAY23
MAY23
MAY23
JUN23
JUN23
JUN23
JUN23
JUL23
JUL23
JUL23
JUL23
JUL23
JUL23
JUL23
AUG23
AUG23
AUG23
AUG23
AUG23
SEP23
SEP23
SEP23
OCT22
SEP23
OCT23
OCT23
OCT23
OCT23
OCT23
NOV23
NOV23
NOV23
NOV23
DEC23
DEC23
DEC23
DEC23
DEC23
DEC23
DEC23
DEC23
DEC23
DEC23
DEC23
DEC23
DEC23
JAN24
JAN24
JAN24
JAN24
FEB24
FEB24
FEB24
FEB24
MAR24
MAR24
PCB CODE
16111192
24110224
01112221
07101221
CSE220701
CSE220704
08111221
08111222
10110221
SC6658
01101231
01101232
09103231
09103232
05104231
04110221
08101231
04103231
08103231
CSE220602A
04106231
CSE221001
CSE220902B
18105231/2
06101231
06101232
CSE230101C
CSE230102
04105231
09105231
18106231
04106181
04106182
15110231
01108231
01108232
01109231
24105231
04105223
04105222
04107222
06107231
24108231
24108232
24108233
24108234
04108231/2
10111231
SC6868
SC6866
01111221
01111222
01111223
10109231
10109232
10109233
18101231
18101241
18101242
18101243
18101244
18101245
18101246
19101241
19101242
07111231
07111232
01110231
01110232
09101241
09101242
16102241
16102242
Price
$2.50
$5.00
$10.00
$5.00
$5.00
$5.00
$12.50
$12.50
$10.00
$10.00
$2.50
$5.00
$5.00
$10.00
$10.00
$10.00
$5.00
$5.00
$4.00
$2.50
$12.50
$5.00
$5.00
$5.00
$1.50
$4.00
$5.00
$5.00
$5.00
$2.50
$2.50
$5.00
$7.50
$12.50
$2.50
$2.50
$10.00
$5.00
$10.00
$2.50
$2.50
$5.00
$5.00
$5.00
$5.00
$5.00
$10.00
$2.50
$2.50
$5.00
$5.00
$5.00
$3.00
$5.00
$2.50
$2.50
$5.00
$2.00
$2.00
$2.00
$1.00
$3.00
$5.00
$12.50
$7.50
$2.50
$2.50
$7.50
$7.50
$5.00
$2.50
$5.00
$2.50
For a complete list, go to siliconchip.com.au/Shop/8
PRINTED CIRCUIT BOARD TO SUIT PROJECT
PICO DIGITAL VIDEO TERMINAL
↳ FRONT PANEL FOR ALTRONICS H0190 (BLACK)
↳ FRONT PANEL FOR ALTRONICS H0191 (BLACK)
WII NUNCHUK RGB LIGHT DRIVER (BLACK)
ARDUINO FOR ARDUINIANS (PACK OF SIX PCBS)
↳ PROJECT 27 PCB
SKILL TESTER 9000
PICO GAMER
ESP32-CAM BACKPACK
WIFI DDS FUNCTION GENERATOR
10MHz to 1MHz / 1Hz FREQUENCY DIVIDER (BLUE)
FAN SPEED CONTROLLER MK2
ESR TEST TWEEZERS (SET OF FOUR, WHITE)
DC SUPPLY PROTECTOR (ADJUSTABLE SMD)
↳ ADJUSTABLE THROUGH-HOLE
↳ FIXED THROUGH-HOLE
USB-C SERIAL ADAPTOR (BLACK)
AUTOMATIC LQ METER MAIN
AUTOMATIC LQ METER FRONT PANEL (BLACK)
180-230V DC MOTOR SPEED CONTROLLER
STYLOCLONE (CASE VERSION)
↳ STANDALONE VERSION
DUAL MINI LED DICE (THROUGH-HOLE LEDs)
↳ SMD LEDs
GUITAR PICKGUARD (FENDER JAZZ BASS)
↳ J&D T-STYLE BASS
↳ MUSIC MAN STINGRAY BASS
↳ FENDER TELECASTER
COMPACT OLED CLOCK & TIMER
USB MIXED-SIGNAL LOGIC ANALYSER (PicoMSA)
DISCRETE IDEAL BRIDGE RECTIFIER (TH)
↳ SMD VERSION
MICROMITE EXPLORE-40 (BLUE)
PICO BACKPACK AUDIO BREAKOUT (with conns.)
8-CHANNEL LEARNING IR REMOTE (BLUE)
3D PRINTER FILAMENT DRYER
DUAL-RAIL LOAD PROTECTOR
VARIABLE SPEED DRIVE Mk2 (BLACK)
FLEXIDICE (RED, PAIR OF PCBs)
SURF SOUND SIMULATOR (BLUE)
COMPACT HIFI HEADPHONE AMP (BLUE)
CAPACITOR DISCHARGER
PICO COMPUTER
↳ FRONT PANEL (BLACK)
↳ PWM AUDIO MODULE
DIGITAL CAPACITANCE METER
BATTERY MODEL RAILWAY TRANSMITTER
↳ THROUGH-HOLE (TH) RECEIVER
↳ SMD RECEIVER
↳ CHARGER
5MHZ 40A CURRENT PROBE (BLACK)
USB PROGRAMMABLE FREQUENCY DIVIDER
HIGH-BANDWIDTH DIFFERENTIAL PROBE
NFC IR KEYFOB TRANSMITTER
POWER LCR METER
WAVEFORM GENERATOR
PICO 2 AUDIO ANALYSER (BLACK)
PICO/2/COMPUTER
↳ FRONT & REAR PANELS (BLACK)
ROTATING LIGHT (BLACK)
433MHZ TRANSMITTER
VERSATILE BATTERY CHECKER
↳ FRONT PANEL (BLACK, 0.8mm)
TOOL SAFETY TIMER
RGB LED ANALOG CLOCK (BLACK)
USB POWER ADAPTOR (BLACK, 1mm)
HWS SOLAR DIVERTER PCB & INSULATING PANELS
SSB SHORTWAVE RECEIVER PCB SET
↳ FRONT PANEL (BLACK)
433MHz RECEIVER
DATE
MAR24
MAR24
MAR24
MAR24
MAR24
MAR24
APR24
APR24
APR24
MAY24
MAY24
MAY24
JUN24
JUN24
JUN24
JUN24
JUN24
JUL24
JUL24
JUL24
AUG24
AUG24
AUG24
AUG24
SEP24
SEP24
SEP24
SEP24
SEP24
SEP24
SEP24
SEP24
OCT24
OCT24
OCT24
OCT24
OCT24
NOV24
NOV24
NOV24
DEC24
DEC24
DEC24
DEC24
DEC24
JAN25
JAN25
JAN25
JAN25
JAN25
JAN25
FEB25
FEB25
FEB25
MAR25
MAR25
MAR25
APR25
APR25
APR25
APR25
MAY25
MAY25
MAY25
MAY25
MAY25
JUN25
JUN25
JUN25
JUN25
PCB CODE
Price
07112231
$5.00
07112232
$2.50
07112233
$2.50
16103241
$20.00
SC6903
$20.00
SC6904
$7.50
08101241
$15.00
08104241
$10.00
07102241
$5.00
04104241
$10.00
04112231
$2.50
10104241
$5.00
SC6963
$10.00
08106241
$2.50
08106242
$2.50
08106243
$2.50
24106241
$2.50
CSE240203A $5.00
CSE240204A $5.00
11104241
$15.00
23106241
$10.00
23106242
$12.50
08103241
$2.50
08103242
$2.50
23109241
$10.00
23109242
$10.00
23109243
$10.00
23109244
$5.00
19101231
$5.00
04109241
$7.50
18108241
$5.00
18108242
$2.50
07106241
$2.50
07101222
$2.50
15108241
$7.50
28110241
$7.50
18109241
$5.00
11111241
$15.00
08107241/2 $5.00
01111241
$10.00
01103241
$7.50
9047-01
$5.00
07112234
$5.00
07112235
$2.50
07112238
$2.50
04111241
$5.00
09110241
$2.50
09110242
$2.50
09110243
$2.50
09110244
$2.50
9049-01
$5.00
04108241
$5.00
9015-D
$5.00
15109231
$2.50
04103251
$10.00
04104251
$5.00
04107231
$5.00
07104251
$5.00
07104252/3 $10.00
09101251
$2.50
15103251
$2.50
11104251
$5.00
11104252
$7.50
10104251
$5.00
19101251
$15.00
18101251
$2.50
18110241
$20.00
CSE250202-3 $15.00
CSE250204 $7.50
15103252
$2.50
SMARTPROBE
↳ SWD PROGRAMMING ADAPTOR
JUL25
JUL25
P9054-04
P9045-A
NEW PCBs
$5.00
$2.50
We also sell the Silicon Chip PDFs on USB, RTV&H USB, Vintage Radio USB and more at siliconchip.com.au/Shop/3
ASK SILICON CHIP
Got a technical problem? Can’t understand a piece of jargon or some technical principle? Drop us a line
and we’ll answer your question. Send your email to silicon<at>siliconchip.com.au
Querying the Versatile
Battery Checker
Regarding the Versatile Battery
Checker project in the May 2025 issue
(siliconchip.au/Article/18121), should
the last line of the article (Nulling the
wiring resistance) read “... then trim
the value to 5mW”? A known-good
high-CCA car starter battery should be
around 4.5-5mW. Also, will the Versatile Battery Checker be made as a kit
by any of the usual Australian electronics suppliers?
Great magazine, as always. Keep up
the good work. (L. P., Ascot Vale, Vic)
● We can expand and clarify on
that section of article. Let’s say that
the raw, unadjusted reading from a
known-good high-CCA car starter
battery is 15mW. If we know that the
battery is responsible for about 5mW
of that, the wiring can be assumed to
measure 10mW. Thus, the correction
value should be entered as 10mW.
A subsequent raw reading from the
same battery will be 15mW. The 10mW
correction factor will then be subtracted, correctly displaying the actual
battery impedance of 5mW.
We are offering a complete kit (see
siliconchip.au/Shop/20/7465) and it
has been very popular. So much so
that we have struggled to keep up with
the demand.
Can Pico 2 W be used
for Pico 2 Computer?
The April 2025 Pico 2 Computer
project (siliconchip.au/Article/17939)
looks interesting, but it includes no
mention of whether the Pico 2 W (the
wireless version) would be a drop-in
upgrade for only a few dollars more.
It seems like a shame where a simple swap can make such a difference,
especially where WiFi or Bluetooth
connectivity can make or break a
project.
It would appear (on superficial
research) that backward compatibility would be maintained for software
between the different versions. Will
100
Silicon Chip
the Silicon Chip shop offer both boards
as options, or just offer the 2 W version
as the preferred option?
As an avid reader since the first
issue, there is something each month
to keep me interested and it expands
my knowledge.
The use of a powerful microcomputer as a drop-in module reminds me
of the cries of heresy that the introduction of ICs brought to the electronics
world. (B. B., Darley, Vic)
● Geoff Graham responds: you
cannot use the Pico 2 W in the Pico
2 Computer, primarily because the
HDMI and WiFi/Internet features both
push the Pico 2 to the limit in different
ways. For example, HDMI requires a
high clock speed, while WiFi/internet
requires a complex protocol stack with
reliable hardware interrupts.
It is just not practical (at this time)
to try to squeeze all of these into the
one package. Also, they are designed
for different uses; the HDMI version
is intended as a ‘boot to BASIC computer’, while the Pico 2W version is
mainly for use as an embedded controller.
Diagnosing solder joints
on Pico 2 Computer
I just bought a kit for the Pico 2
Computer from your shop and I seem
to have a problem. The Pico 2 won’t
go into bootloader mode. It’s not the
cables or my computer because, using
the same cable, a Pico 1 happily goes
into bootloader mode and shows up
as a memory device. Yes, I’m holding BOOTSEL down as I connect the
USB cable.
I’m annoyed at myself for not loading the firmware before I soldered it
onto the main board so I could have
at least determined that the Pico 2
was OK, but it is too late for that. I
have checked my soldering and there
don’t seem to be any solder bridges
or dry joints.
I know you can’t easily diagnose
it from what I’ve told you, but if others have the same or similar problem,
Australia's electronics magazine
there might be some hope of a resolution. (N. B., Medowie, NSW)
● In our experience, the Pico modules are very reliable. We’ve only seen
one soldering fault on a USB socket
once, and that would not affect you
even if it were the case since you’re
not using the onboard socket.
We asked Geoff Graham what he
thought about this and he wrote: I
have never seen a Pico that cannot be
bootloaded. I would be very surprised
if the Pico 2 is faulty.
More likely, it is a soldering fault in
one of three possible areas:
1. The test pads on the Pico 2 have
not been successfully soldered to the
holes on the PCB. This is the most
likely fault.
2. There is a soldering fault in the
USB socket used for programming.
3. One or more pads on the Pico 2
are not soldered correctly – this is also
a common fault.
I suggest removing the programming jumpers and trying to squeeze
a USB plug into the USB socket of
the Pico 2. This is difficult, but if it
can be done, the reader should then
be able to program the Pico 2 in the
usual way (hold down BOOT during
power on). If that works, it will prove
that the Pico 2 is OK, and it’s likely a
soldering problem.
N. B. later confirmed that resoldering the pads on the underside of
the Pico 2 board while inserting short
lengths of wire fixed it.
Pico 2 Computer has
faulty USB hub chip
I got some Pico 2 Computer boards
made by JLCPCB using the BOM and
PCB files downloaded from Geoff Graham’s website. On powering it up, the
red USBHUB LED lights up. The green
LED that switches 5V power to the USB
ports is not on, so the other four LEDs
will not light either.
There is +5V at the source and gate
terminals of Mosfet Q1 (MDD2301).
The drain is at 0V. Both boards do
exactly the same thing. Everything
siliconchip.com.au
else seems to be working correctly:
video, the real-time clock etc. (B. P.,
Rostrevor, SA)
● Geoff Graham responds: this
sounds like a problem that we have
been dealing with recently. It appears
that there is a bad batch of CH334F
chips out there. If the chips on your
board are batch number 1163FD43,
they will work. If they are 13122E20,
they won’t.
The fix is to remove resistors R54
and R55. This disables the over-current
protection feature in the CH334F
(which is the cause of the problem).
The USB ports are still protected by
the resettable fuse, so this change will
not cause a problem.
Speaker wire with
aluminium conductors
I have a technical question about
tinned copper cables that you may be
able to answer.
I bought some loudspeaker cables
recently from Bunnings – one of the
multicore wires in the insulated cable
pair was a bright shiny copper colour,
and it soldered easily. The other wire
looked like a shiny tinned copper wire,
but it would not solder. I tried 60/40
solder, lead-free solder and even silver solder, but none worked.
I wonder if you have any experience
in these matters. I have been soldering
electronics for decades; I wonder what
is wrong. (E. U., Castle Hill, NSW)
● It sounds like aluminium wire,
which is very hard to solder. We took
a guess, searched the Bunnings website and came up with Antsig 18GA
Speaker Cable – 30m, which seems
very cheap at $17.65. If you look under
Specifications, it states, Material: PVC,
Copper, Aluminium.
So it seems that one conductor is
copper, and the other is aluminium,
presumably because it’s cheaper (and
lighter) than copper. It will probably
work OK if you make a mechanical
connection to it (eg, using a screw
connector).
Current Probe doesn’t
have a CAT III rating
I have built several Silicon Chip
projects that interact with the mains.
One thing I usually do is change any
banana posts and sockets to those with
a CAT III safety rating.
The 40A Current Probe (January
siliconchip.com.au
How was the TV Pattern Generator EEPROM programmed?
Dr Hugo Holden’s article in the January 2025 issue, about retrieving data from old
microcontrollers (siliconchip.au/Article/17609), piqued my interest.
I built the Colour TV Pattern Generator from your June & July 1997 issues
(siliconchip.au/Series/215). It is still working well; it would be a shame if the
EPROM failed. I am curious to know what programming setup was used at the time.
I have looked on eBay etc and noticed that there are some EPROM programmers
available, but they don’t appear to support the device used in the colour pattern
generator (TMS27C512).
I realise that the technology is dated now, but it would be interesting to build
a project that runs on modern PC software that can talk to these old chips. As
mentioned in Dr Holden’s article, it can save some specialised gear from the scrap
heap. (G. C., Toormina, NSW)
● Our memories are a bit hazy after nearly 30 years, but we think we made a
basic EPROM programmer controlled by a computer running a BASIC program.
The device support list for the popular TL866II programmer includes the
TMS27C512 and we think the newer versions like the XGecu T48 programmer
we reviewed in the April 2023 issue (siliconchip.au/Article/15735) can program
them too.
Alternatively, you could use the EPROM programmer by Jim Rowe published in
the November 2002 to February 2003 issues and updated in June 2004 (siliconchip.
au/Series/110). The software could be run within DOSBox, with Windows installed
within that. You would need a Centronics interface to USB converter for the EPROM
programmer to computer interface. Having said that, using the TL866II/T48 will
probably be easier and more future-proof.
2025; siliconchip.au/Article/17605) is
an excellent project but was let down
by any lack of a CAT III interface. Some
minor tweaks would lift the project
into the professional category. (R. M.,
Currumbin Valley, Qld)
● Thanks for the feedback; it is
always good to get reader comments
and constructive suggestions. The
Current Probe was not designed to be
used in CAT III environments, which
are described as:
• Equipment in fixed installations,
such as switchgear and polyphase
motors
• Bus & feeder in industrial plants
• Feeders and short branch circuits,
distribution panel devices
• Lighting systems in larger buildings
• Appliance outlets with short connections to service entrance
Most Silicon Chip readers will use
the device in a domestic setting with
appropriate current-limiting devices,
like circuit breakers and fuses. To
design a device for CAT III requires
much more than CAT III rated connectors – it encompasses the entire
design, including the case, which
would need to withstand very high
energy transients.
Specifying CAT III connectors alone
could be misleading (in that readers
may think the overall device meets the
CAT III standard when it doesn’t) and
Australia's electronics magazine
would make it unnecessarily expensive. Just changing the binding posts
to CAT III rated types would almost
double the cost of construction!
That said, there should be no problem using such connectors provided
they are mechanically compatible.
The ones you suggested have a slightly
lower current rating than those we
specified (32A vs 35A), which you
will need to keep this in mind. Either
way, we don’t advise using the Current Probe in an industrial or commercial setting.
Controlling Digital Pot
with IR Remote Keyfob
It has been great fun building and
subsequently enjoying some of Silicon Chip’s audio designs, in particular, two different powered loudspeaker
projects. Adding IR remote control
using Phil Prosser’s Digital Volume
Control (March 2023; siliconchip.au/
Article/15693) to all three of my builds
added some most welcome functionality.
The only (admittedly small but
pesky) negative to the completed setups has been the bulk of the recommended universal remotes, since only
three buttons are needed. When I spotted the miniature IR Keyfob Remote
project in the February 2025 issue, I
of course ordered the kit to play with.
July 2025 101
As one that is far more comfortable
with hardware than software, configuring the handy little device to work with
the Digital Pots has been beyond me.
I followed the instructions in the article and managed to install the NDEF
text record for NEC, but am at a loss
to know how to find the codes that the
Digital Pots respond to.
I would be very grateful for instructions on how to install the two Philips
RC5 codes that are programmed into
the Digital Pot’s PIC16F15214. I need
both because two of my speaker systems are close by. Each digital volume control has been reset to respond
uniquely, as described on page 38 of
the March 2023 issue. (R. M., Ivanhoe, Vic)
● We had a look through the Digital
Volume Control source code to find the
IR codes it used and confirmed they
were reasonable using the web page at
https://w.wiki/DWYG
The code accepts RC5 decimal
addresses 0 (TV) and 16 (preamp/
receiver), with RC5 commands 13
(mute), 16 (volume up) and 17 (volume down). The defaults correspond
to the following NDEF entries for the
IR Remote Keyfob:
5,0,16
5,0,17
5,0,13
The alternative codes are:
5,16,16
5,16,17
5,16,13
R. M. later confirmed that these
codes work as expected.
Finding instructions for
Short Circuits project
I built the Jiminy Cricket project
quite some years ago when the instructions appeared in Silicon Chip magazine.
I have bought a new kit but was surprised to find no instructions with it.
Could you please tell me what past
issue of Silicon Chip had the instructions in it, as I have kept all my old
magazines but don’t have an overarching index for them. (R. K., Pukekohe,
New Zealand)
● We have published several articles on electronic crickets but none
of them were called “Jiminy Cricket”.
Our only cricket kit is for Silicon
Chirp, which was from the April 2023
issue (siliconchip.au/Article/15738).
“Jiminy Cricket” is from Jaycar’s
102
Silicon Chip
“Short Circuits Volume 2” book, and
they make and sell a kit for it (Cat
KJ8224). As far as we know, the only
place you can find the instructions for
that kit are in the Short Circuits Volume 2 book, which is listed as still
available from Jaycar (Cat BJ8504).
While Silicon Chip did some of the
production work on that book, Jaycar
remains the exclusive source for Short
Circuits kits and books.
Testing USB-C cables
with Cable Tester
Regarding the USB Cable Tester
from the November & December 2021
issues (siliconchip.au/Series/374),
thank you for a fantastic and useful
project. I enjoyed building it, although
I found it challenging to solder
extremely small components. It seems
to be functioning as intended, identifying the quality and resistance of each
USB cable sample.
However, all my USB-A to USB-C
cables report (on the 2nd row of the
display) either POWER ONLY or USB
2.0, depending on the orientation of
the USB-C connector. I see the same
result on my USB-C to USB-C cables,
in one direction only; otherwise, they
always display POWER ONLY.
I would expect a reading like USB
3.2 etc, since most of my cables are of
higher quality (eg, Comsol high speed).
Maybe it’s OK, because in your article, you describe how USB-C leads
only have one D+/D- pair (the wires
required for a legacy USB 2.0 connection) but they can be plugged in one of
two ways. So some orientations do not
detect this pair. Therefore, that is the
best result I can expect from a USB-A
to a USB-C connection?
That still doesn’t explain why my
USB-C to USB-C behaves the same
way, though. Could there be a problem with my tester’s soldering? Thanks
again for a great publication. (J. C.,
Mount Waverley, Vic)
● Your observations appear to be
consistent with a working USB Cable
Tester. We delved into testing USB-C
cables on the last page (p93) of the USB
Cable Tester Project article, part two
(December 2021). As you’ve found, the
USB-C plug needs to be tried both ways
to get a meaningful result. USB-C to
USB-C cables need to have both ends
tried both ways, ie, four combinations.
The USB-C specification says that
only one USB-2.0 pair is provided in
Australia's electronics magazine
USB-C cables, and you can see that
in the circuit diagram (Fig.1, p30,
November 2021). Only one of the USB2.0 pairs are connected in CON4 and
CON6; thus, only one combination
will work.
With the limited number of pins
(only 40!) available on the PIC microcontroller, we chose this arrangement
over shorting the pins together, since
it would allow the cable condition to
be better understood by trying different rotations.
With regards to the USB-C to USB-C
cable, we think this is due to USB’s
confusing terminology.
USB low-speed and USB full-speed
are both USB-1.1 designations, referring to 1.5Mb/s and 12Mb/s signalling
rates, respectively. USB high-speed
was introduced with USB-2.0 and
refers to 480Mb/s. The various USB 3.0
(and subsequent 3.1 and 3.2) signalling
rates are referred to as SuperSpeed
and SuperSpeed+ (5Gb/s and higher).
In other words, a high-speed cable,
like you describe, is almost certainly
only USB-2.0 compliant. If you test a
SuperSpeed USB-C to USB-C cable,
you should get a different result.
Snooping on I2C data
with a micro is difficult
Some time ago, I built the USB Digital & SPI Interface Board from the
November 2018 issue (siliconchip.au/
Article/11299). I would like to use it to
monitor an I2C conversation between
an Arduino Nano and an Si5351 clock
generator board, but it appears to take
control of the bus and hold the clock
line low. Is there a way to configure it
into a slave listening-only mode?
I have also found that it sends out
characters as they are typed into Tera
Term without waiting for a line feed.
Is this normal, or is Tera Term not the
best interface for the board? (M. H.,
Mordialloc, Vic)
● The software, as written, does not
allow the Interface Board to act like
a slave, only a master. So the short
answer to the first question is: no.
The software could be rewritten,
but the problem with a slave I2C monitor is that it has to run at the speed
dictated by the master and catch all
clock edges, while a master decides
what should happen. The PIC16F1455
is a fairly modest 8-bit chip with a
12MHz maximum clock frequency, so
continued on page 104
siliconchip.com.au
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Silicon Chip magazine regularly describes projects which employ a mains power supply or produce high voltage. All such projects
should be considered dangerous or even lethal if not used safely. Readers are warned that high voltage wiring should be carried
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When working on these projects use extreme care to ensure that you do not accidentally come into contact with mains AC
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you are advised not to attempt work on them. Silicon Chip Publications Pty Ltd disclaims any liability for damages should anyone
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siliconchip.com.au
Australia's electronics magazine
July 2025 103
Advertising Index
Altronics.................................29-32
Blackmagic Design....................... 7
Dave Thompson........................ 103
DigiKey Electronics....................... 3
Emona Instruments.................. IBC
Hare & Forbes............................. 11
Jaycar.................. IFC, 12-13, 44-45
Keith Rippon Kit Assembly....... 103
Lazer Security........................... 103
LD Electronics........................... 103
LEDsales................................... 103
Microchip Technology.............OBC
Mouser Electronics....................... 4
OurPCB Australia.......................... 5
PCBWay......................................... 9
PMD Way................................... 103
SC Micromite Explore 40............ 56
SC Mains Sequencer................ 103
Silicon Chip Shop.................97-99
Silicon Chip Songbird................ 52
Silicon Chip Subscriptions........ 53
The Loudspeaker Kit.com.......... 10
Wagner Electronics..................... 85
YUKI KP-480 machine.............. 103
we don’t think that is possible unless
the clock provided by the master is
quite slow.
For example, we used a Raspberry
Pi Pico running at 133MHz+ to create
an I2C monitor device to capture the
output of an I2C OLED, to emulate
its display. Even then, the I2C master
needed to be slowed substantially to
capture the data successfully.
The immediate output behaviour is
normal since the Interface Board delivers the data as soon as it is received.
Something like the Arduino IDE’s
serial monitor will only send data
when the line ending is entered, so
that is an option if you want such
behaviour.
Protection diodes on
amplifier outputs
Regarding Electronic Australia’s
Playmaster and Silicon Chip’s audio
amplifiers, I am curious why there
are no back-EMF protective diodes
connected between the emitters and
collectors on the output transistors.
They are used with many commercial
amplifiers, including Naim, Denon etc.
I have assembled many EA and
Silicon Chip amplifiers over many
years for friends and myself. (D. B.,
via email)
● We have included such diodes in
most of our amplifiers since November 2012, when they were used in
the Classic-D amplifier (siliconchip.
au/Series/17). Since then, they can
be seen in the Ultra-LD Mk.4 amplifier from August 2015 (siliconchip.
au/Series/289), the SC200 in January
Errata and on-sale data for the next issue
2017 (siliconchip.au/Series/308) and
the 500W Amplifier from April 2022
(siliconchip.au/Series/380).
These diodes are necessary when
the amplifier is used to drive a transformer, as used for 70V and 100V line
connected loudspeakers. The diodes
are not strictly required while the
amplifier is operating within its linear
range, where the negative feedback has
control of the amplifier output.
Only when the amplifier is in clipping, where the output operation is
beyond the limits of feedback control, will the protection diodes come
into effect and clamp any back-EMF.
This only occurs when the amplifier
is used with a significantly inductive load.
Our earlier amplifiers without the
protection diodes were long-lasting
and reliable. Including these diodes
in later designs is part of the evolution
of semiconductor power amplifiers,
beginning in the Electronics Australia days in the 1960s.
With continued improvements
over the decades, our amplifiers have
become some of the best performers
ever published, rivalling the best commercial amplifiers.
Generally, including these diodes
doesn’t seem to hurt and they may
be beneficial in some circumstances.
Earlier amplifiers would have omitted them due to their cost, but these
days suitable diodes will not break
the bank, so we might as well specify them.
DIY inverters are no
longer worthwhile
Next Issue: the August 2025 issue is due on sale in newsagents by Monday, July
28th. Expect postal delivery of subscription copies in Australia between July 25th
and August 15th.
I saw advertisements in two old
issues of Silicon Chip for 24V DC to
240V AC inverter kits from Altronics.
I also found an old Rod Irving kit for
a 2kW 24V DC to 240V AC inverter
from 1992-1993. Are there more recent
projects for inverter kits? (R. S., Chifley, NSW)
● While it may have been worthwhile to build your own inverter back
in the early 1990s, today it definitely
isn’t. Basic commercial inverters can
be found under $30. A 150W inverter
will cost you around $50, while $99
will get you a 400-500W inverter. You
can get a 2kW inverter for under $200
from many sources.
Anything we design would cost
more than that in just parts, and you
SC
would still have to build it.
Australia's electronics magazine
siliconchip.com.au
Vintage Radio – Emerson 888, May 2025: there are two mistakes in the
redrawn circuit diagram (Fig.1). R6 is shown connected to the wrong end of
T2’s secondary; it should connect to the lower side that goes to the base of
TR2. Separately, the junction of C10 & R10 should connect to the base of TR3
(the bottom end of T3’s secondary), rather than the top of T3’s secondary.
Power LCR Meter, March & April 2025: in Fig.8 on p36 of the March issue, the
SI and SCK pins of IC5 are numbered incorrectly. SI is pin 6 and SCK is pin 5.
Mains Power-Up Sequencer, February, March & July 2024: if using the Mains
Detect Input feature, the 10μF electrolytic capacitor next to pin 4 of IC10
should be installed, even though it is in the Current Detection section. This
prevents false triggering due to EMI pickup.
Reciprocal Frequency Counter, July 2023: the lowest frequency the Counter
can measure is 2Hz, not 10mHz. Also, below 10Hz, its readings may not be
very accurate.
104
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